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WO1992016085A1 - Source d'alimentation electrique a facteur de puissance eleve, dotee de moyens de commande permettant de suivre le trajet de la tension alternative d'entree - Google Patents

Source d'alimentation electrique a facteur de puissance eleve, dotee de moyens de commande permettant de suivre le trajet de la tension alternative d'entree Download PDF

Info

Publication number
WO1992016085A1
WO1992016085A1 PCT/US1992/001752 US9201752W WO9216085A1 WO 1992016085 A1 WO1992016085 A1 WO 1992016085A1 US 9201752 W US9201752 W US 9201752W WO 9216085 A1 WO9216085 A1 WO 9216085A1
Authority
WO
WIPO (PCT)
Prior art keywords
voltage
power supply
producing
control
control signal
Prior art date
Application number
PCT/US1992/001752
Other languages
English (en)
Inventor
John G. Konopka
Dennis Stephens
Original Assignee
Motorola Lighting, Inc.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Motorola Lighting, Inc. filed Critical Motorola Lighting, Inc.
Priority to KR1019930702696A priority Critical patent/KR970002285B1/ko
Priority to BR9205729A priority patent/BR9205729A/pt
Priority to JP4507858A priority patent/JPH06507777A/ja
Publication of WO1992016085A1 publication Critical patent/WO1992016085A1/fr

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC using static converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • This invention relates to power supplies, and particularly, though not exclusively, to voltage boost power supplies for use in driving gas discharge lamps such as fluorescent lamps .
  • Gas discharge lamps are non-linear, negative resistance loads and so need to be driven from a ballast circuit.
  • a ballast circuit typically incorporates a power supply which is itself supplied from a low frequency supply (e.g. a 60Hz utility mains) .
  • Such a ballast circuit should ideally exhibit a high power factor (the ratio of the output power and input power, i.e. the ratio of the power delivered to the lamps and the power taken from the mains) and low harmonic distortion (introduction into the mains of frequencies different from the mains frequency) .
  • ballast circuits use a power supply which boosts the mains voltage, e.g. at lamp start-up, by employing a boost inductor whose current is controlled by a switch (e.g. a field-effect transistor) which is in turn controlled by a pulse-width-modulated (PWM) signal.
  • PWM pulse-width-modulated
  • the switch turns OFF, the inductive current in the boost inductor generates an increased voltage.
  • the PWM signal is typically generated in a current-mode control integrated circuit (IC) .
  • IC current-mode control integrated circuit
  • a power supply comprising: an input for receiving an alternating supply voltage; an output for producing a voltage derived from the supply voltage; voltage producing means coupled between the input and the output for carrying a current and for producing a voltage therefrom; switch means for controlling the current carried by the voltage producing means; and control signal generating means for producing a pulsed control signal to control the switch means so as to control the current carried by the voltage producing means and thereby control the voltage produced thereby, the improvement comprising modulating means coupled between the input and the control signal generating means for modulating the frequency of the control signal in accordance with the alternating supply voltage whereby the frequency of the control signal has a maximum value when the magnitude of the alternating supply voltage is a maximum so as to cause the current carried by the voltage producing means to have a waveform which approximates to that of the alternating supply voltage.
  • the power supply produces low harmonic distortion and exhibits a high power factor.
  • a power supply for converting an AC voltage into a DC voltage
  • said power supply having: a full wave rectifier coupled to said AC voltage, means for producing a pulse width modulated signal, said means having a control input, and means controlled by said signal for producing said DC voltage, the improvement comprising means for coupling said control input to the full wave rectifier to cause the frequency of said pulse width modulated signal to vary in accordance with the magnitude of said AC voltage whereby the frequency of said pulse width modulated signal has a maximum value when the magnitude of said AC voltage is a maximum, thereby obtaining high power factor and low harmonic distortion.
  • FIG. 1 shows a partially block-schematic circuit diagram of the fluorescent lamp drive circuit
  • FIG. 2 shows the waveform of the supply line voltage applied to the circuit
  • FIG. 3 shows the waveform of the line current drawn by the circuit
  • FIG. 4 shows the waveform of line current drawn by a modified form of the circuit, not incorporating the present invention.
  • a circuit 100 for driving three fluorescent lamps 102, 104, 106, has two input terminals 108, 110 for receiving thereacross an AC supply voltage of approximately 277V at a frequency of 60Hz.
  • a full-wave rectifying bridge circuit 112 has two input nodes 114, 116 connected respectively to the input terminals 108, 110, and has two output nodes 118, 120.
  • the output node 118 of the bridge 112 is connected to a ground voltage rail 122.
  • a cored inductor 124 (having an inductance of approximately 4.5mH) has one end connected to the output node 120 of the bridge 112, and has its other end connected to a node 126.
  • a field effect transistor (FET) 128 (of the type BUZ90) has its drain electrode connected to the node 126.
  • the field effect transistor (FET) 128 has its source electrode connected, via a resistor 130 (having a value of approximately 1.6 ⁇ ) , to the ground voltage rail 122.
  • a diode 132 (of the type MUR160) has its anode connected to the node 126 and has its cathode connected to an output terminal 134.
  • the ground voltage rail 122 is connected to an output terminal 136.
  • An integrating capacitor 137 is connected between the output terminals 134 and 136.
  • a resistor 138 (having a resistance of approximately 2M ⁇ ) is connected between the output node 120 of the bridge 112 and a node 140.
  • a capacitor 142 (having a capacitance of approximately 0.0039 ⁇ F) is connected between the node 140 and the ground voltage rail 122.
  • a current-mode control integrated circuit (IC) 144 (of the type AS3845, available from ASTEC Semiconductor) has its R ⁇ /C ⁇ input (pin 4) connected to the node 140.
  • the current mode control IC 144 has its V RE G output (pin 8) connected, via a resistor 146 (having a resistance of approximately 10K ⁇ ) , to the node 140 and connected, via a capacitor 148 (having a capacitance of approximately 0.22 ⁇ F) to the ground voltage rail 122.
  • the current mode control IC 144 has its control signal output (pin 6) connected, via a resistor 150 (having a resistance of approximately 20 ⁇ ) , to the gate electrode of the FET 128.
  • the gate electrode of the FET 128 is also connected, via a resistor 152 (having a resistance of approximately 22K ⁇ ) , to the ground voltage rail 122.
  • Two resistors 154, 156 (having respective resistances of approximately 974K ⁇ and 5.36K ⁇ ) are connected in series, via an intermediate node 158, between the output terminal 134 and the ground voltage rail 122.
  • the current mode control IC 144 has its V FB input (pin 2) connected to the node 158 via a resistor 160 (having a resistance of approximately 47K ⁇ ) .
  • the current mode control IC 144 has its COMP output (pin 1) connected to its V FB input (pin 2) via a series-connected resistor 162 (having a resistance of approximately 100K ⁇ ) and capacitor 164 (having a capacitance of approximately O.l ⁇ F) .
  • the current mode control IC 144 has its current sense input (pin 3) connected to the ground voltage rail 122 via a capacitor 166 (having a capacitance of approximately 470pF) and to the source electrode of the FET 128 via a resistor 168 (having a resistance of approximately 1K ⁇ ) .
  • the current mode control IC 144 has its V c c input (pin 7) connected to the bridge rectifier output node 120 via a resistor 170 (having a resistance of approximately 240K ⁇ ) and connected to the ground voltage rail 122 via a capacitor 172 (having a capacitance of approximately 100 ⁇ F) .
  • the current mode control IC 144 has its GND input (pin 5) connected to the ground voltage rail 122.
  • the power supply output terminals 134 and 136 are connected to a half-bridge inverter 174, whose output is connected to a series-resonant tank circuit 176.
  • the output of the tank circuit is connected, via a transformer 178, to the three fluorescent lamps which are connected in series.
  • the composition and operation of ballast sub-components 174, 176 and 178 are well-known in the art and need not be further described herein. Such sub-components are described more fully in, for example, U.S. patent application no. 07/636,833, which is assigned to the same assignee as the present application, and the disclosure of which is hereby incorporated by reference.
  • the bridge 112 In operation of the circuit of FIG. 1, with a voltage of 277V, 60Hz (as shown in FIG. 2) applied across the input terminals 108 and 110, the bridge 112 produces between the node 120 and the ground voltage rail 122 a unipolar, full-wave rectified, DC voltage having a frequency of 120Hz.
  • the FET 128 When the FET 128 is enabled to conduct, substantially the whole of this unipolar DC voltage appears across the inductor 124, and causes current to flow through the inductor.
  • this inductive current causes the voltage across the inductor to increase. This increased voltage is applied through the diode 132 to the output terminal 134.
  • the increased voltage between the output terminals 134 and 136 charges the capacitor 137 which powers the inverter 174, the series-resonant tank circuit 176 and the transformer 178 to drive the three series-connected fluorescent lamps 102, 104, 106.
  • the switching between enablement and disablement of the FET 128 is controlled by the control signal (output from pin 6) of the current mode control IC 144.
  • the IC s control signal output is in the form of a pulse-width modulated signal, during whose mark intervals the FET is switched ON to enable conduction of current and during whose space intervals the FET is switched OFF to disable conduction of current.
  • the IC's pulse-width modulated control signal at pin 6 has a nominal mark/space ratio of unity, producing a nominal 50% duty cycle.
  • the frequency of the IC's pulse-width modulated control signal and the voltage at the node 120 determine the current drawn from the supply line.
  • the nominal frequency of the PWM control signal produced at pin 6 of the IC 144 which is determined by the product of the values of the resistor 146 and the capacitor 142, is approximately 23KHz.
  • the frequency of the pulse-width modulated control signal produced at pin 6 of the IC is forced to vary in response to the AC line voltage (whose waveform is shown in FIG. 2) applied across the input terminals 108 and 110.
  • the current applied to pin 4 of the IC 144 increases and causes the frequency of the PWM control signal output at pin 6 of the IC to increase.
  • the frequency of the PWM control signal output at pin 6 of the IC has its minimum, nominal value of approximately 23KHz when the bridge output voltage has its minimum, zero value, and the frequency of the PWM control signal output at pin 6 of the IC has its maximum value of approximately 43KHz when the bridge output voltage has its peak value.
  • the frequency of the ICs PWM control signal is proportionately reduced.
  • the frequency of the pulse-width modulated control signal produced at pin 6 of the IC 144 determines the current drawn from the bridge 112 and hence from the AC supply line.
  • the line current is caused to vary in this way by the connection provided between the node 120 and the node 140 by the resistor 138, which causes a modulating signal from the output of the rectifier bridge 112 to be applied to the frequency determining input RT/C-J at pin 4 of the IC 144. If the resistor 138 were removed, the frequency of the PWM output signal produced at pin 6 of the IC 144 would remain constant at approximately 23KHz, and the line current drawn by the circuit would be of the form shown in FIG. 4.
  • the waveform of FIG. 4 is noticeably less sinusoidal than that of FIG. 3, particularly in the regions marked 180 around the zero-crossings of the waveform. These deviations from sinusoidal shape in the waveform of FIG. 4 would manifest themselves as increased THD and decreased power factor, both of which are substantially avoided in the circuit 100 whose line current waveform is shown in FIG. 3.
  • the degree of modulation provided of the PWM output signal of the IC 144 could be varied by varying the value of the resistor 138 and additionally or alternatively by inserting a resistor (not shown) in parallel with the capacitor 142 between the node 140 and ground voltage rail. Such variation could be used to provide greater or lesser compensation for the non-sinusoidal regions 180 shown in FIG. 4, as desired.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Circuit Arrangements For Discharge Lamps (AREA)
  • Inverter Devices (AREA)
  • Rectifiers (AREA)
  • Dc-Dc Converters (AREA)

Abstract

L'invention se rapporte à une source d'alimentation électrique à fonction de survolteur, qui est conçue pour être utilisée dans le tube ballast (100) d'une lampe fluorescente et qui comprend: une inductance (170) couplée entre une entrée de tension source alternative (108, 110) et une sortie (134, 136), un commutateur (128) qui commande le courant transporté par l'inductance, et un circuit intégré (144) de commande du mode de courant, destiné à produire un signal de commande à modulation d'impulsions en largeur, qui commande le commutateur, afin de commander le courant transporté par l'inductance et par conséquent la tension traversant l'inductance. Le circuit intégré de commande du mode de courant est couplé (138) à l'entrée, pour que la fréquence du signal de commande soit modulée en fonction de la tension source alternative, de sorte que la fréquence du signal de commande présente une valeur maximale lorsque l'amplitude de la tension source alternative est à son niveau maximum. Cette source d'alimentation électrique se caractérise ainsi par des distorsions harmoniques réduites et par un facteur de puissance accru.
PCT/US1992/001752 1991-03-07 1992-03-06 Source d'alimentation electrique a facteur de puissance eleve, dotee de moyens de commande permettant de suivre le trajet de la tension alternative d'entree WO1992016085A1 (fr)

Priority Applications (3)

Application Number Priority Date Filing Date Title
KR1019930702696A KR970002285B1 (ko) 1991-03-07 1992-03-06 입력 교류 흐름을 제어하므로써 고전력 요소를 구비하는 전원장치
BR9205729A BR9205729A (pt) 1991-03-07 1992-03-06 Fornecimento de energia, e lastro para acionar lâmpadas de descarga de gás
JP4507858A JPH06507777A (ja) 1991-03-07 1992-03-06 交流供給入力に追従する制御機能と共に高い出力係数を有する電源

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
US66583091A 1991-03-07 1991-03-07
US665,830 1991-03-07

Publications (1)

Publication Number Publication Date
WO1992016085A1 true WO1992016085A1 (fr) 1992-09-17

Family

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Family Applications (1)

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PCT/US1992/001752 WO1992016085A1 (fr) 1991-03-07 1992-03-06 Source d'alimentation electrique a facteur de puissance eleve, dotee de moyens de commande permettant de suivre le trajet de la tension alternative d'entree

Country Status (8)

Country Link
EP (1) EP0577704A1 (fr)
JP (1) JPH06507777A (fr)
KR (1) KR970002285B1 (fr)
CN (1) CN1064955A (fr)
BR (1) BR9205729A (fr)
CA (1) CA2103542A1 (fr)
MX (1) MX9201010A (fr)
WO (1) WO1992016085A1 (fr)

Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO1997034464A1 (fr) * 1996-03-18 1997-09-25 Gad Products, S.A. De C.V. Ballast electronique auto-regule a rendement eleve et a courbe caracteristique unique pour l'exploitation de lampes a vapeur de sodium a haute pression
WO1999005776A1 (fr) * 1997-07-25 1999-02-04 Siemens Ag Österreich Convertisseur a decoupage
FR2773279A1 (fr) * 1997-12-31 1999-07-02 Motorola Inc Procede, dispositif, telephone et station de base pour fournir un convertisseur de puissance de poursuite pour signaux variables
EP0989784A1 (fr) * 1998-09-23 2000-03-29 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH Circuit et procédé pour le calibrage et l'opération des alimentations MLI pour lampes à baisse voltage
GB2366395A (en) * 2000-09-05 2002-03-06 Minebea Electronics Active power factor correction

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
KR101142271B1 (ko) * 2010-01-08 2012-05-11 (주) 트랜스마그넷 채널사인 형광램프용 전자식 안정기

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE3233655A1 (de) * 1981-09-11 1983-05-05 Zumtobel AG, 6850 Dornbirn Elektronisches vorschaltgeraet fuer eine leuchtstoff- oder gasentladungsroehre
US4677366A (en) * 1986-05-12 1987-06-30 Pioneer Research, Inc. Unity power factor power supply
US4870327A (en) * 1987-07-27 1989-09-26 Avtech Corporation High frequency, electronic fluorescent lamp ballast
EP0352983A1 (fr) * 1988-07-25 1990-01-31 Astec International Limited Facteur de puissance
US4920302A (en) * 1987-01-27 1990-04-24 Zenith Electronics Corporation Fluorescent lamp power supply
EP0380033A2 (fr) * 1989-01-25 1990-08-01 Siemens Aktiengesellschaft Disposition de circuit pour alimentation à découpage à récuperation à circuit résonnant

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE3233655A1 (de) * 1981-09-11 1983-05-05 Zumtobel AG, 6850 Dornbirn Elektronisches vorschaltgeraet fuer eine leuchtstoff- oder gasentladungsroehre
US4677366A (en) * 1986-05-12 1987-06-30 Pioneer Research, Inc. Unity power factor power supply
US4920302A (en) * 1987-01-27 1990-04-24 Zenith Electronics Corporation Fluorescent lamp power supply
US4870327A (en) * 1987-07-27 1989-09-26 Avtech Corporation High frequency, electronic fluorescent lamp ballast
EP0352983A1 (fr) * 1988-07-25 1990-01-31 Astec International Limited Facteur de puissance
EP0380033A2 (fr) * 1989-01-25 1990-08-01 Siemens Aktiengesellschaft Disposition de circuit pour alimentation à découpage à récuperation à circuit résonnant

Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO1997034464A1 (fr) * 1996-03-18 1997-09-25 Gad Products, S.A. De C.V. Ballast electronique auto-regule a rendement eleve et a courbe caracteristique unique pour l'exploitation de lampes a vapeur de sodium a haute pression
US6137238A (en) * 1996-03-18 2000-10-24 Alvarez; Eduardo Salman High-efficiency self-regulated electronic ballast with a single characteristic curve for operating high-pressure sodium vapor lamps
WO1999005776A1 (fr) * 1997-07-25 1999-02-04 Siemens Ag Österreich Convertisseur a decoupage
FR2773279A1 (fr) * 1997-12-31 1999-07-02 Motorola Inc Procede, dispositif, telephone et station de base pour fournir un convertisseur de puissance de poursuite pour signaux variables
EP0989784A1 (fr) * 1998-09-23 2000-03-29 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH Circuit et procédé pour le calibrage et l'opération des alimentations MLI pour lampes à baisse voltage
GB2366395A (en) * 2000-09-05 2002-03-06 Minebea Electronics Active power factor correction
GB2366395B (en) * 2000-09-05 2002-09-11 Minebea Electronics Active power factor correction

Also Published As

Publication number Publication date
BR9205729A (pt) 1994-08-02
MX9201010A (es) 1992-09-01
KR970002285B1 (ko) 1997-02-27
CA2103542A1 (fr) 1992-09-17
CN1064955A (zh) 1992-09-30
EP0577704A1 (fr) 1994-01-12
JPH06507777A (ja) 1994-09-01

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