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WO2018167952A1 - Dispositif d'antenne réseau adaptative - Google Patents

Dispositif d'antenne réseau adaptative Download PDF

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Publication number
WO2018167952A1
WO2018167952A1 PCT/JP2017/010957 JP2017010957W WO2018167952A1 WO 2018167952 A1 WO2018167952 A1 WO 2018167952A1 JP 2017010957 W JP2017010957 W JP 2017010957W WO 2018167952 A1 WO2018167952 A1 WO 2018167952A1
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WO
WIPO (PCT)
Prior art keywords
calculation unit
null
correlation matrix
weight
calculated
Prior art date
Application number
PCT/JP2017/010957
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English (en)
Japanese (ja)
Inventor
龍平 高橋
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三菱電機株式会社
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Publication date
Application filed by 三菱電機株式会社 filed Critical 三菱電機株式会社
Priority to PCT/JP2017/010957 priority Critical patent/WO2018167952A1/fr
Priority to JP2019505652A priority patent/JP6573745B2/ja
Priority to GB1910715.0A priority patent/GB2573909B/en
Publication of WO2018167952A1 publication Critical patent/WO2018167952A1/fr

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    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/2605—Array of radiating elements provided with a feedback control over the element weights, e.g. adaptive arrays
    • H01Q3/2611—Means for null steering; Adaptive interference nulling
    • H01Q3/2617—Array of identical elements
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/36—Means for anti-jamming, e.g. ECCM, i.e. electronic counter-counter measures
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/2605—Array of radiating elements provided with a feedback control over the element weights, e.g. adaptive arrays
    • H01Q3/2611—Means for null steering; Adaptive interference nulling
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H04B7/0617—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal for beam forming
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
    • H04B7/0837—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station using pre-detection combining
    • H04B7/0842—Weighted combining
    • H04B7/0848—Joint weighting
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
    • H04B7/0837—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station using pre-detection combining
    • H04B7/0842—Weighted combining
    • H04B7/086—Weighted combining using weights depending on external parameters, e.g. direction of arrival [DOA], predetermined weights or beamforming
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
    • H04B7/0868—Hybrid systems, i.e. switching and combining
    • H04B7/088—Hybrid systems, i.e. switching and combining using beam selection

Definitions

  • the present invention relates to an adaptive array antenna apparatus that multiplies a plurality of signals respectively received by a plurality of subarray antennas by a weighting factor and synthesizes the plurality of signals after the weighting factor multiplication.
  • the radar apparatus is mounted on a platform such as an aircraft, and may be operated in an environment where an interference wave arrives.
  • the antenna device included in the radar device forms an adaptive beam by an array antenna in which a plurality of subarray antennas are arranged. At this time, the antenna device suppresses the interference wave included in the received signal of the array antenna, and improves the SJNR (Signal to Jamming and Noise Ratio) of the target signal related to the target to be observed.
  • the adaptive weight is determined so that a null is formed in the arrival direction of.
  • the adaptive weight is a weight coefficient for a plurality of signals respectively received by a plurality of subarray antennas.
  • the determination of the adaptive weight by the antenna device is performed by the following method, for example.
  • the antenna device temporarily stops a beam transmitted from the array antenna, and uses a plurality of signals respectively received by a plurality of subarray antennas as interference signal during a listening period in which the beam is not transmitted. get.
  • the antenna device determines an adaptive weight from the acquired interference wave signal so that a null is formed in the arrival direction of the interference wave.
  • the arrival direction of the disturbing wave does not change unless the source of the disturbing wave moves.
  • the radar device including the antenna device or the source of the interference wave is moving, the arrival direction of the interference wave changes. For this reason, even if the antenna apparatus determines an adaptive weight in which a null is formed in the arrival direction of the jamming wave during the listening period, the jamming is performed in a short time until the beam transmission is resumed from the array antenna.
  • the direction of arrival of waves changes. That is, the arrival direction of the interference wave in the listening period and the arrival direction of the interference wave in the beam transmission period, which is a period in which the beam is transmitted after the listening period ends, are in different directions.
  • Non-Patent Document 1 discloses an antenna device that performs a process of widening a null formed by an adaptive weight determined during a listening period in order to avoid the influence of a null shift.
  • the conventional antenna apparatus performs a process of expanding the width of the null formed by the adaptive weight, but does not appropriately set the extension width of the null width based on the change in the arrival direction of the disturbing wave. For this reason, a large change may occur in which the arrival direction of the interference wave exceeds the widened null width. Thus, when the change of the arrival direction of the jamming wave is large, there is a problem that the jamming wave included in the received signal of the array antenna cannot be suppressed.
  • the present invention has been made to solve the above-described problems, and an antenna device capable of suppressing the interference wave included in the received signal of the array antenna even if the arrival direction of the interference wave greatly changes.
  • the purpose is to obtain.
  • the antenna device includes an array antenna in which a plurality of subarray antennas including one or more element antennas are arranged, and a plurality of subarray antennas during a listening period in which a beam is not transmitted from the array antenna. Interference waves in the listening period from a plurality of signals received respectively and a plurality of signals respectively received by a plurality of subarray antennas during a beam transmission period in which a beam is transmitted after the end of the listening period.
  • a null shift estimation unit that estimates a null shift, which is a change between the arrival direction of the interference wave and the arrival direction of the jamming wave in the beam transmission period, and a plurality of null shift estimations based on the null shift estimated by the null shift estimation unit.
  • a compensation weight calculating unit that calculates a compensation weight for compensating for the null shift, and the beam forming unit applies a plurality of signals respectively received by the plurality of subarray antennas during the beam transmission period to the compensation weight calculating unit.
  • the calculated compensation weights are multiplied to synthesize a plurality of signals after the compensation weight multiplication.
  • the interference in the listening period from the plurality of signals respectively received by the plurality of subarray antennas during the listening period and the plurality of signals respectively received by the plurality of subarray antennas during the beam transmission period.
  • a null shift estimation unit that estimates a null shift that is a change between the arrival direction of the wave and the arrival direction of the disturbing wave in the beam transmission period, and the compensation weight calculation unit is based on the null shift estimated by the null shift estimation unit.
  • the compensation weight for compensating for the null shift is calculated as the weighting factor for the plurality of signals respectively received by the plurality of subarray antennas, the arrival direction of the interference wave greatly changes. Also has the effect of suppressing interfering waves contained in the received signal of the array antenna
  • FIG. 1 is a block diagram showing an adaptive array antenna apparatus according to Embodiment 1 of the present invention.
  • FIG. 2 is a hardware configuration diagram showing the signal processing device 2 of the adaptive array antenna device according to Embodiment 1 of the present invention.
  • the subarray antenna 1-m is an antenna including at least one element antenna.
  • the signal processing device 2 includes a null shift estimation unit 11, a compensation weight calculation unit 12, and a beam forming unit 13, and multiplies a plurality of signals respectively received by the M subarray antennas 1-m by weighting factors.
  • FIG. 1 for simplification of the drawing, a receiver for detecting a signal received by the subarray antenna 1-m, a converter for converting the received signal of the receiver from an analog signal to a digital signal, and the like are omitted. Actually, a receiver and a converter are provided. For this reason, the null shift estimation unit 11 and the beam forming unit 13 are given digital received signals corresponding to the signals received by the M subarray antennas 1-m.
  • a received signal vector including M digital received signals is shown.
  • the null shift estimation unit 11 is realized by, for example, a null shift estimation circuit 21 shown in FIG.
  • the null shift estimation unit 11 receives M digital received signals corresponding to M signals respectively received by the M subarray antennas 1-m during a listening period in which a beam is not transmitted from the array antenna 1. get.
  • the null shift estimation unit 11 corresponds to the M signals respectively received by the M subarray antennas 1-m during the beam transmission period, which is a period during which the beam after the listening period ends is transmitted.
  • M digital received signals are acquired.
  • the null shift estimation unit 11 uses the M digital reception signals during the listening period and the M digital reception signals during the beam transmission period, and the arrival direction of the interference wave during the listening period and the arrival of the interference wave during the beam transmission period.
  • the process which estimates the null shift which is a change with a direction is implemented.
  • the beam transmission period includes a period in which the array antenna 1 receives a beam in addition to a period in which the array antenna 1 transmits a beam.
  • the compensation weight calculation unit 12 is realized by, for example, a compensation weight calculation circuit 22 illustrated in FIG. Based on the null shift estimated by the null shift estimation unit 11, the compensation weight calculation unit 12 receives M signals corresponding to M signals respectively received by the M subarray antennas 1-m during the beam transmission period. As a weighting factor for the digital received signal, a process of calculating a compensation weight for compensating for a null shift is performed.
  • the beam forming unit 13 is realized by, for example, a beam forming circuit 23 shown in FIG.
  • the beam forming unit 13 includes M multipliers 14-m and adders 15, and M corresponding to M signals respectively received by the M subarray antennas 1-m during the beam transmission period.
  • a process of multiplying the digital reception signals by the compensation weight calculated by the compensation weight calculation unit 12 and combining the M digital reception signals after the compensation weight multiplication is performed.
  • the multiplier 14-m multiplies the digital reception signal corresponding to the signal received by the sub-array antenna 1-m during the beam transmission period by the compensation weight calculated by the compensation weight calculation unit 12, and after the compensation weight multiplication.
  • the digital reception signal is output to the adder 15.
  • the adder 15 combines the digital reception signals after multiplication of the M compensation weights output from the M multipliers 14-m, and outputs the combined digital reception signal as a reception beam.
  • each of the null shift estimation unit 11, the compensation weight calculation unit 12, and the beam forming unit 13, which are components of the signal processing device 2, is realized by dedicated hardware as shown in FIG. is doing. That is, what is realized by the null shift estimation circuit 21, the compensation weight calculation circuit 22, and the beam forming circuit 23 is assumed.
  • the null shift estimation circuit 21, the compensation weight calculation circuit 22, and the beam forming circuit 23 are, for example, a single circuit, a composite circuit, a programmed processor, a processor programmed in parallel, an ASIC (Application Specific Integrated Circuit), an FPGA (Field-). Programmable Gate Array) or a combination thereof.
  • the components of the signal processing device 2 are not limited to those realized by dedicated hardware, and the signal processing device 2 is realized by software, firmware, or a combination of software and firmware. May be.
  • Software or firmware is stored as a program in the memory of a computer.
  • the computer means hardware that executes a program, and includes, for example, a CPU (Central Processing Unit), a central processing unit, a processing unit, an arithmetic unit, a microprocessor, a microcomputer, a processor, a DSP (Digital Signal Processor), and the like. .
  • FIG. 3 is a hardware configuration diagram of a computer when the signal processing device 2 is realized by software or firmware.
  • a program for causing the computer to execute the processing procedures of the null shift estimation unit 11, the compensation weight calculation unit 12, and the beam forming unit 13 is stored in the memory 31 of the computer.
  • the computer processor 32 may execute a program stored in the memory 31.
  • FIG. 6 is a flowchart showing a processing procedure when the signal processing device 2 is realized by software or firmware.
  • the memory 31 of the computer is, for example, a RAM (Random Access Memory), a ROM (Read Only Memory), a flash memory, an EPROM (Erasable Programmable Read Only Memory Memory, or an EEPROM (Electrically Erasable Memory).
  • a volatile semiconductor memory, a magnetic disk, a flexible disk, an optical disk, a compact disk, a mini disk, a DVD (Digital Versatile Disc), and the like are applicable.
  • FIG. 4 is a block diagram showing a null shift estimation unit 11 of the adaptive array antenna apparatus according to Embodiment 1 of the present invention.
  • the first correlation matrix calculation unit 41 calculates the interference wave from M digital received signals corresponding to M signals respectively received by the M subarray antennas 1-m during the listening period. A process of calculating a correlation matrix is performed.
  • the vector calculation unit 42 scans the scanning direction of the interference wave using the weight constraint vector for scanning the main beam direction of the beam and the interference matrix of the interference wave calculated by the first correlation matrix calculation unit 41.
  • a process of calculating a weight vector for performing is performed. That is, the vector calculation unit 42 is a diagonal matrix having a path difference phase component due to the difference between the main beam direction and the scan direction in the diagonal terms, the weight constraint vector, and the disturbance calculated by the first correlation matrix calculation unit 41.
  • a process of calculating a weight vector is performed by multiplying the wave correlation matrix.
  • the second correlation matrix calculation unit 43 receives the received signal of the array antenna 1 from the M digital received signals corresponding to the M signals respectively received by the M subarray antennas 1-m during the beam transmission period. The process which calculates the correlation matrix of is implemented.
  • the evaluation function calculation unit 44 uses the weight vector calculated by the vector calculation unit 42 and the correlation matrix of the received signal calculated by the second correlation matrix calculation unit 43 to calculate an evaluation function used for estimation of the null shift. Perform the calculation process.
  • the null deviation estimation processing unit 45 uses the evaluation function calculated by the evaluation function calculation unit 44 to perform processing for estimating a null deviation.
  • FIG. 5 is a block diagram showing the compensation weight calculation unit 12 of the adaptive array antenna apparatus according to Embodiment 1 of the present invention.
  • the CMT matrix calculation unit 51 calculates a CMT (Covariance Matrix Tape) matrix that is a matrix for setting a null width from the null shift estimated by the null shift estimation processing unit 45 of the null shift estimation unit 11.
  • the weight calculation processing unit 52 includes a compensation type correlation matrix calculation unit 53 and a compensation type weight calculation unit 54.
  • the weight calculation processing unit 52 compensates for the null shift from the CMT matrix calculated by the CMT matrix calculation unit 51 and the interference matrix correlation matrix calculated by the first correlation matrix calculation unit 41 of the null shift estimation unit 11. The process which calculates the compensation weight to perform is implemented.
  • the compensation type correlation matrix calculation unit 53 calculates a null shift from the CMT matrix calculated by the CMT matrix calculation unit 51 and the interference matrix correlation matrix calculated by the first correlation matrix calculation unit 41 of the null shift estimation unit 11. A process of calculating a compensation type correlation matrix is performed.
  • the compensation weight calculation unit 54 performs a process of calculating a compensation weight for compensating for the null shift from the weight constraint vector and the null shift compensation correlation matrix calculated by the compensation correlation matrix calculation unit 53.
  • the signal processing device 2 detects M signals respectively received by the M subarray antennas 1-m, and converts each of the detected M signals from analog signals to digital signals.
  • the null shift estimation unit 11 and the beam forming unit 13 of the signal processing device 2 are provided with a received signal vector including digital received signals that are M digital signals that have been converted.
  • a received signal vector x 0 (t) shown in the following equation (1) is given to the null shift estimating unit 11 and the beam forming unit 13.
  • t is time
  • a J (u 0 (k) ) is the arrival direction
  • u 0 (k) [u 0 (k) , v 0 (k) ] T
  • T is a symbol indicating transposition
  • j k (t) is the complex amplitude of the k-th jamming wave
  • n 0 (t) is the receiver noise vector.
  • the reception signal during the listening period is represented by the following equation (2).
  • the interference matrix correlation matrix R 0 is calculated from the vector x 0 (t) (step ST1 in FIG. 6).
  • E [•] is a symbol indicating an ensemble average with respect to •.
  • H is a symbol indicating Hermitian transposition.
  • a finite number of received signal vectors x 0 (t) at different times t in the listening period are used.
  • the first correlation matrix calculator 41 outputs the calculated interference matrix correlation matrix R 0 to the vector calculator 42 and the compensation-type correlation matrix calculator 53 of the compensation weight calculator 12.
  • Vector calculating unit 42 obtains the scan direction u of the disturbance, determining the scanning direction u and the main beam direction u s difference diagonal matrix having a path difference phase component in the diagonal section by D of (u-u s) .
  • the main beam direction u s is in the beam transmission period after the listening period ends, the direction of the main beam in the beam transmitted from the array antenna 1.
  • the vector calculation unit 42 obtained during beam transmission period after the listening period has ended, the wait constraint vector a to scan the main beam direction u s of the beam transmitted from the array antenna 1 (u s) To do.
  • the vector calculation unit 42 is output from the diagonal matrix D (u ⁇ u s ), the weight constraint vector a (u s ), and the first correlation matrix calculation unit 41 as shown in the following equation (3).
  • the weight vector w (u) for scanning the scanning direction u of the interference wave is calculated by multiplying the interference wave correlation matrix R 0 (step ST2 in FIG. 6).
  • ⁇ is a normalization coefficient set in advance.
  • the vector calculation unit 42 outputs the calculated weight vector w (u) to the evaluation function calculation unit 44.
  • a received signal vector x (t) shown in the following equation (4) is given to the null shift estimation unit 11 and the beam forming unit 13.
  • s (t) is the target signal
  • a s is the steering vector for the direction of arrival of the target signal s (t)
  • n (t ) is the receiver noise vector
  • receiver noise vector n The characteristics of t) are the same as the characteristics of the receiver noise vector n 0 (t) during the listening period.
  • u 0 (k) + ⁇ u k is the arrival direction of the k-th jamming wave in the beam transmission period, and is shifted from the arrival direction of the k-th jamming wave in the listening period.
  • ⁇ u k [ ⁇ u k , ⁇ v k ] T is the difference between the arrival direction of the kth jamming wave in the beam transmission period and the arrival direction of the kth jamming wave in the listening period.
  • the second correlation matrix calculation unit 43 of the null shift estimation unit 11 is given the received signal vector x (t) during the beam transmission period after the end of the listening period, as shown in the following equation (5).
  • the correlation matrix R x of the received signal of the array antenna 1 is calculated from the received signal vector x (t) during the beam transmission period (step ST3 in FIG. 6).
  • the second correlation matrix calculation unit 43 outputs the calculated correlation matrix R x of the received signal to the evaluation function calculation unit 44.
  • the evaluation function calculation unit 44 of the null shift estimation unit 11 calculates the weight vector w (u) output from the vector calculation unit 42 and the correlation matrix R x of the reception signal output from the second correlation matrix calculation unit 43.
  • an evaluation function P (u) used for estimation of null shift is calculated (step ST4 in FIG. 6).
  • W H (u) R x w (u) which is the denominator of Equation (6), is the scanning output power of the beam by the weight vector w (u).
  • the weight vector w (u) is a weight vector for scanning the weight vector w (u s ) in the main beam direction u s in the interference wave scanning direction u, and thus the weight vector w (u).
  • the null for the direction of arrival u of the jamming wave formed by is also scanned.
  • the weight vector w (u), the scanning direction u is if u s + .delta.u k, to form a null in the direction of u 0 (k) + ⁇ u k .
  • This null the formation direction u 0 (k) + ⁇ u k coincides with the arrival direction u 0 (k) + ⁇ u k of the k-th interference wave contained in the correlation matrix R x of the received signal, w H (u s + ⁇ u k) R x w (u s + ⁇ u k) of the k-th included in the interference wave power is minimized.
  • the evaluation function calculation unit 44 outputs the calculated evaluation function P (u) to the null deviation estimation processing unit 45.
  • the null deviation estimation processing unit 45 of the null deviation estimation unit 11 estimates the null deviation using the evaluation function P (u) output from the evaluation function calculation unit 44, and calculates the compensation value of the estimated null deviation value ⁇ u hat. It outputs to the part 12 (step ST5 of FIG. 6).
  • the vector calculation unit 42 may calculate the weight vector w (u) for scanning the scanning direction u of the interference wave by the following equation (7) instead of the equation (3).
  • D ⁇ is a diagonal matrix having a difference beam forming taper in the diagonal terms.
  • w (u) is a weight vector forming a null in an arrival direction u and the main beam direction u s jammer.
  • target signal coming from the vicinity of the main beam direction u s is suppressed, it is included in w H (u s + ⁇ u k ) R x w (u s + ⁇ u k) The power of the target signal is reduced.
  • u corresponding to the peak function value is a candidate for null shift
  • the peak function value ⁇ u corresponding to u is the null deviation estimated value ⁇ u hat.
  • the CMT matrix T CMT for setting the null width is calculated using the estimated null deviation estimated value ⁇ u hat (step ST6 in FIG. 6).
  • the set null width ⁇ u based on the CMT matrix T CMT is determined as shown in the following formula (9) based on the null deviation estimated value ⁇ u hat.
  • k u and k v are arbitrary coefficients, and are values set in advance according to the taper used in beam forming, regardless of the estimated null shift estimated value ⁇ u hat.
  • the CMT matrix calculation unit 51 outputs the calculated CMT matrix T CMT to the compensation type correlation matrix calculation unit 53.
  • a null shift compensation type correlation matrix R is calculated from the interference matrix correlation matrix R0 output from the correlation matrix calculation unit 41 (step ST7 in FIG. 6).
  • a double circle symbol is a symbol indicating a Hadamard product that performs multiplication of matrix elements of the CMT matrix T CMT and the correlation matrix R 0 of the interference wave.
  • the compensation type correlation matrix calculation unit 53 outputs the calculated null shift compensation type correlation matrix R to the compensation type weight calculation unit 54.
  • the compensation weight calculation unit 54 uses the weight constraint vector a (u s ) and the null deviation compensation type correlation matrix R output from the compensation type correlation matrix calculation unit 53 as shown in the following equation (11). Then, a compensation weight vector w A indicating a compensation weight for compensating for the null shift is calculated (step ST8 in FIG. 6).
  • ⁇ is a normalization coefficient.
  • the compensation weight calculation unit 54 outputs the calculated compensation weight vector w A to the beam forming unit 13.
  • the beam forming unit 13 compensates the reception signal vector x (t) as shown in the following equation (12).
  • a reception beam y (t) is calculated by multiplying the weight vector w A and combining the reception signal vector x (t) after the compensation weight multiplication (step ST9 in FIG. 6).
  • the M multipliers 14-m in the beam forming unit 13 are included in the compensation weight vector w A in the digital reception signal related to the subarray antenna 1-m included in the reception signal vector x (t).
  • the compensation weights related to the sub-array antenna 1 -m are multiplied, and the digital received signal after the compensation weight multiplication is output to the adder 15.
  • the adder 15 of the beam forming unit 13 combines the M digital reception signals output from the M multipliers 14-m, and outputs the combined digital reception signal as a reception beam y (t).
  • reception signal vector x (t) is multiplied by the compensation weight vector w A , a null having a set null width ⁇ u is formed in the reception beam y (t) with the arrival direction u 0 of the disturbing wave as the center. ing.
  • a plurality of signals respectively received by the M subarray antennas 1-m during the listening period and M subarray antennas during the beam transmission period a null shift estimation unit 11 that estimates a null shift, which is a change between the arrival direction of the interference wave in the listening period and the arrival direction of the interference wave in the beam transmission period, from the plurality of signals respectively received by 1-m;
  • the compensation weight calculation unit 12 uses a null coefficient as a weighting factor for a plurality of signals respectively received by the M subarray antennas 1-m during the beam transmission period. Since the compensation weight for compensating for the deviation is calculated, the array antenna 1 can be used even if the arrival direction of the disturbing wave changes greatly. An effect that can suppress interference waves in the received signal.
  • the compensation weight calculation unit 12 includes the CMT matrix calculation unit 51, and uses the CMT matrix T CMT calculated by the CMT matrix calculation unit 51 to provide a compensation weight indicating a compensation weight for compensating for a null shift.
  • An example of calculating the vector w A is shown.
  • the compensation weight calculation unit 12 calculates a compensation weight vector w A indicating a compensation weight for compensating for a null shift without using the CMT matrix TCMT .
  • FIG. 7 is a block diagram showing a compensation weight calculation unit 12 of the adaptive array antenna apparatus according to Embodiment 2 of the present invention.
  • the weight calculation processing unit 55 includes a compensation type correlation matrix calculation unit 56 and a compensation type weight calculation unit 54.
  • the compensation-type correlation matrix calculation unit 56 calculates the null shift estimated by the null shift estimation processing unit 45 of the null shift estimation unit 11 and the interference wave calculated by the first correlation matrix calculation unit 41 of the null shift estimation unit 11. A process of calculating a null shift compensation type correlation matrix is performed from the correlation matrix.
  • ⁇ u k [ ⁇ u k , ⁇ v k ] T.
  • the received signal vector x (t) shown in the following equation (13) is converted to the null shift estimation unit 11 and the beam forming unit 13.
  • u 0 (k) + ⁇ u is the arrival direction of the kth jamming wave in the beam transmission period, and is shifted from the arrival direction of the kth jamming wave in the listening period.
  • the second correlation matrix calculation unit 43 of the null shift estimation unit 11 is given the beam transmission as in the first embodiment when the reception signal vector x (t) during the beam transmission period shown in the equation (13) is given.
  • a correlation matrix R x of the reception signal of the array antenna 1 is calculated from the reception signal vector x (t) during the period.
  • the second correlation matrix calculation unit 43 outputs the calculated correlation matrix R x of the received signal to the evaluation function calculation unit 44.
  • the evaluation function calculation unit 44 of the null shift estimation unit 11 calculates the weight vector w (u) output from the vector calculation unit 42 and the correlation matrix R x of the reception signal output from the second correlation matrix calculation unit 43.
  • the evaluation function P (u) used for estimating the null shift is calculated.
  • W H (u) R x w (u) which is the denominator of Equation (6), is the scanning output power of the beam by the weight vector w (u).
  • the weight vector w (u) is a weight vector for scanning the weight vector w (u s ) in the main beam direction u s in the interference wave scanning direction u, and thus the weight vector w (u).
  • the null for the direction of arrival u of the jamming wave formed by is also scanned.
  • the weight vector w (u) forms a null in the direction of u 0 (k) + ⁇ u if the scan direction u is u s + ⁇ u. Since the direction u 0 (k) + ⁇ u forming this null coincides with the arrival direction u 0 (k) + ⁇ u of the k-th jamming wave included in the correlation matrix R x of the received signal, w H (u s + .delta.u) power R x w (u s + ⁇ u k-th interference wave contained in) is minimized.
  • the estimated value is ⁇ u hat.
  • the evaluation function calculation unit 44 outputs the calculated evaluation function P (u) to the null deviation estimation processing unit 45.
  • the null deviation estimation processing unit 45 of the null deviation estimation unit 11 estimates the null deviation by using the evaluation function P (u) output from the evaluation function calculation unit 44, as in the first embodiment, and the null deviation. Is output to the compensation weight calculation unit 12.
  • the compensation-type correlation matrix calculation unit 56 of the compensation weight calculation unit 12 outputs the null shift estimated value ⁇ u hat output from the null shift estimation processing unit 45 of the null shift estimation unit 11 and the first correlation matrix calculation unit 41.
  • a null shift compensation type correlation matrix R 0 ′ is calculated from the correlation matrix R 0 of the disturbed wave.
  • the compensation type correlation matrix calculation unit 56 outputs the calculated null shift compensation type correlation matrix R 0 ′ to the compensation type weight calculation unit 54.
  • the interference matrix correlation matrix R 0 calculated by the first correlation matrix calculator 41 can be expressed as the following Expression (14).
  • a 0 is a matrix in which K steering vectors a J (u 0 (k) ) are arranged, J is a correlation matrix of j k (t), and ⁇ 2 is receiver noise power.
  • the interference matrix R 0 ′ of the interference wave during the beam transmission period can be expressed as the following equation (15).
  • the interference matrix correlation matrix R 0 ′ during the beam transmission period corresponds to a null shift compensation correlation matrix.
  • a 0 ′ is a matrix in which K steering vectors a J (u 0 (k) + ⁇ u) are arranged.
  • the compensation weight calculation unit 54 calculates the weight constraint vector a (u s ) and the null deviation compensation correlation matrix R 0 ′ output from the compensation correlation matrix calculation unit 53 as shown in the following equation (19). Using this, a compensation weight vector w A indicating a compensation weight for compensating for the null shift is calculated.
  • the compensation weight calculation unit 54 outputs the calculated compensation weight vector w A to the beam forming unit 13.
  • the beam forming unit 13 adds the compensation weight vector to the reception signal vector x (t) as in the first embodiment.
  • the reception beam y (t) is calculated by multiplying w A and synthesizing the reception signal vector x (t) after the compensation weight multiplication. Since the reception signal vector x (t) is multiplied by the compensation weight vector w A , a null having a set null width ⁇ u is formed in the reception beam y (t) with the arrival direction u 0 of the disturbing wave as the center. ing.
  • the present invention is suitable for an adaptive array antenna apparatus that multiplies a plurality of signals received by a plurality of subarray antennas by a weighting factor and synthesizes the plurality of signals after the weighting factor multiplication.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Remote Sensing (AREA)
  • Variable-Direction Aerials And Aerial Arrays (AREA)
  • Radar Systems Or Details Thereof (AREA)
  • Radio Transmission System (AREA)

Abstract

La présente invention concerne une unité d'estimation de décalage nul (11) permettant d'estimer un décalage nul correspondant à un changement entre une direction d'arrivée d'un brouillage dans une période d'écoute et une direction d'arrivée d'un brouillage dans une période de transmission de faisceau, à partir d'une pluralité de signaux reçus respectivement par un nombre M d'antennes de sous-réseau (1-m) pendant la période d'écoute et d'une pluralité de signaux reçus respectivement par les M antennes de sous-réseau (1-m) pendant la période de transmission de faisceau. En fonction du décalage nul estimé par l'unité d'estimation de décalage nul (11), une unité de calcul de pondération de compensation (12) calcule une pondération de compensation permettant de compenser un décalage nul, la pondération de compensation servant de facteur de pondération pour la pluralité de signaux reçus respectivement par les M antennes de sous-réseau (1-m) pendant la période de transmission de faisceau.
PCT/JP2017/010957 2017-03-17 2017-03-17 Dispositif d'antenne réseau adaptative WO2018167952A1 (fr)

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