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WO2018163792A1 - Dispositif de conversion de tension continue - Google Patents

Dispositif de conversion de tension continue Download PDF

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Publication number
WO2018163792A1
WO2018163792A1 PCT/JP2018/005834 JP2018005834W WO2018163792A1 WO 2018163792 A1 WO2018163792 A1 WO 2018163792A1 JP 2018005834 W JP2018005834 W JP 2018005834W WO 2018163792 A1 WO2018163792 A1 WO 2018163792A1
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WO
WIPO (PCT)
Prior art keywords
auxiliary
voltage
switch element
voltage converter
connection point
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PCT/JP2018/005834
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English (en)
Japanese (ja)
Inventor
陳　登
貴史 川上
Original Assignee
株式会社オートネットワーク技術研究所
住友電装株式会社
住友電気工業株式会社
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Application filed by 株式会社オートネットワーク技術研究所, 住友電装株式会社, 住友電気工業株式会社 filed Critical 株式会社オートネットワーク技術研究所
Publication of WO2018163792A1 publication Critical patent/WO2018163792A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only

Definitions

  • the technology disclosed in this specification relates to a DC voltage converter, and more particularly, to a DC voltage converter provided with an auxiliary resonance circuit.
  • the energy source of the auxiliary resonance circuit that is, the power source is the output voltage Vout. Since the output voltage Vout is obtained by converting the input voltage Vin, the loss in the auxiliary resonance circuit is also added as a conversion loss. This was not advantageous for improving the efficiency of the converter. Further, in the configuration in which the output voltage Vout is applied to the auxiliary resonance circuit in this way, when the input voltage Vin is converted to the very low output voltage Vout, even if the output voltage Vout is applied to the auxiliary resonance circuit, The voltage at point M in FIG. 1 does not reach the input voltage Vin, and there is a possibility that soft switching (zero voltage switching) of the first main switch S1 cannot be performed. In this case, the switching loss in the first main switch S1 increases.
  • the technology disclosed in the present specification has been completed based on the above-described circumstances, and provides a DC voltage converter capable of maintaining high conversion efficiency when applied to a large-capacity load. To do.
  • a DC voltage converter disclosed in the present specification is a DC voltage converter that converts a DC input voltage applied from a main power source into an output voltage having a predetermined voltage value, and is connected to the main power source.
  • One end of the auxiliary reactor is electrically connected to an auxiliary resonance circuit connected to a first connection point that is a connection point between the first switch element and the low-pass filter, and to the auxiliary resonance circuit and a ground line, and the input
  • An auxiliary voltage applying unit that applies an auxiliary voltage having a constant voltage lower than a voltage value to the auxiliary reactor via the auxiliary switch element; the first connection point; and the ground line.
  • the auxiliary voltage application unit that supplies power to the auxiliary resonance circuit is provided. Therefore, a loss caused by the auxiliary resonance circuit, for example, a switching loss caused by the auxiliary switch element is not added to the switching loss of the first switch element when the input voltage is converted into the output voltage.
  • the first switch element is zero-voltage switched and the auxiliary switch element is zero-current switched. Therefore, according to the direct-current voltage converter of this configuration, high conversion efficiency can be maintained even when applied to a large-capacity load.
  • the reflux unit may be configured by a second switch element that is zero-voltage switched by the switch control unit. According to this configuration, the return period can be appropriately set by on / off control of the second switch element, and the switching loss of the second switch element can be suppressed by zero voltage switching.
  • the DC voltage converter may further include a first parallel capacitor connected in parallel to the first switch element and a second parallel capacitor connected in parallel to the reflux unit. According to this configuration, when the first switch element is turned off, the speed of the potential change at the first connection point in the so-called dead time can be adjusted.
  • the DC voltage converter may further include a first diode connected between a second connection point that is a connection point between the auxiliary reactor and the auxiliary switch element, and the ground line.
  • the first diode can stabilize the potential at the second connection point during the off-period of the auxiliary switch element. That is, when the auxiliary switch element is off and the second switch element is on, when the MOSFET is used as the auxiliary switch element, the potential at the second connection point varies via the parasitic capacitance of the auxiliary switch element. Can be considered. In that case, the fluctuation
  • the auxiliary switch element may be configured by two auxiliary switch elements connected in series that are simultaneously controlled by the switch control unit. According to this configuration, by configuring the auxiliary switch element with two auxiliary switch elements connected in series, the on-resistance as the auxiliary switch element increases. Accordingly, the on-state current flowing when the auxiliary switch element is turned on is reduced, so that the on-resistance loss of the auxiliary switch element is reduced as compared with the case where there is only one auxiliary switch element.
  • the loss (power) is proportional to the square of the current, in this case, the amount of decrease in the on-resistance loss due to the decrease in the on-current is greater than the amount of increase in the on-resistance loss that accompanies the increase in on-resistance. Therefore, on-resistance loss is reduced.
  • the DC voltage converter may further include a second diode connected between a third connection point that is an intermediate connection point of the two auxiliary switch elements and the power supply line.
  • the second diode can stabilize the potential at the third connection point in a period in which one auxiliary switch element close to the auxiliary voltage application unit is off. That is, when one auxiliary switch element is off and the other auxiliary switch element and the second switch element are on, when a MOSFET is used as one auxiliary switch element, the parasitic capacitance of one auxiliary switch element is reduced. Therefore, it is conceivable that the potential at the third connection point varies. In that case, the fluctuation
  • the main power source is composed of a battery composed of a plurality of cells
  • the auxiliary voltage application unit includes an external connection terminal connected to an intermediate potential part of the battery, and the external connection terminal You may make it comprise with the voltage application line which connects the said auxiliary
  • the auxiliary voltage application unit can be formed with a simple configuration without providing an auxiliary power source such as a battery in the apparatus.
  • the auxiliary voltage may have a voltage value that is half or more of the input voltage. According to this configuration, each switch element can be soft-switched reliably by setting the voltage value of the auxiliary voltage to be equal to or lower than the input voltage and equal to or higher than half the input voltage.
  • the DC voltage converter disclosed in this specification can maintain high conversion efficiency when applied to a large-capacity load.
  • FIG. 1 is a schematic circuit diagram illustrating a DC voltage converter according to a first embodiment.
  • Schematic time chart showing the operation of the DC voltage converter Schematic partial circuit diagram showing the current flow of the DC voltage converter
  • Schematic partial circuit diagram showing the current flow of the DC voltage converter Schematic partial circuit diagram showing the current flow of the DC voltage converter
  • Schematic partial circuit diagram showing the current flow of the DC voltage converter Schematic partial circuit diagram showing the current flow of the DC voltage converter
  • the partial circuit diagram which shows the auxiliary voltage application part which concerns on Embodiment 2.
  • the DC voltage converter 10 is a so-called chopper type step-down DC-DC converter, which steps down a DC input voltage Vin applied from a battery as a main power source 40, It is converted into a DC output voltage Vout having a predetermined voltage value.
  • the input voltage Vin is 48V, for example, and the output voltage Vout is 24V, for example.
  • the DC voltage conversion device 10 is arranged for an HV vehicle on which a gasoline engine and a travel motor are mounted, and is applied to a power circuit that supplies power to a large-capacity load 50 such as a travel motor. Is done.
  • the application of the DC voltage converter 10 is not limited to HV vehicles, and is not limited to vehicles.
  • the load to which the DC voltage converter 10 is applied is not necessarily limited to a large capacity load.
  • the present invention is not limited to a step-down DC-DC converter, and can be applied to a step-up DC-DC converter as will be described later.
  • the DC voltage converter 10 includes an internal power line Ls, a first switch element SW1, a first parallel capacitor C1, a switch control unit 11, an auxiliary voltage application unit 12, a low-pass filter 13, and a reflux unit 14. , And an auxiliary resonant circuit 20.
  • the internal power supply line Ls is connected to the battery 40 and supplies the power from the battery 40 to each part of the DC voltage converter 10.
  • the first switch element SW1 is configured by an N-channel MOSFET including a body diode D1.
  • the drain of the first switch element SW1 is connected to the internal power supply line Ls.
  • the first parallel capacitor C1 is connected in parallel to the first switch element SW1.
  • the first parallel capacitor C1 is not limited to an individual element, and may be a parasitic capacitor of the first switch element SW1.
  • the low-pass filter 13 is a well-known filter and includes, for example, a smoothing reactor Lo and a smoothing capacitor Co as shown in FIG.
  • An input terminal 13a (corresponding to one end of the low-pass filter) of the low-pass filter 13 is connected to a source terminal S (corresponding to one end of the first switch element) of the first switch element SW1, and an output terminal 13b of the DC voltage converter 10 is connected. Connected to the output terminal.
  • the low-pass filter 13 receives the potential Vn1 of the first connection point N1, that is, the first connection point voltage Vn1, and outputs the output voltage Vout obtained by smoothing the first connection point voltage Vn1.
  • the reflux unit 14 is connected between the first connection point N1 and the ground line Lg, and is well known.
  • the reflux unit 14 is configured by the second switch element SW2 as shown in FIG.
  • the second switch element SW2 is configured by an N-channel MOSFET including a body diode D2, and is zero-voltage switched by the switch control unit 11.
  • the second parallel capacitor C2 is connected in parallel to the second switch element SW2.
  • the second parallel capacitor C2 can adjust the changing speed of the first connection point voltage Vn1 when the first switch element SW1 and the second switch element SW2 are in the off state, that is, the so-called dead time.
  • the second parallel capacitor C2 is not limited to an individual element, like the first parallel capacitor C1, and may be a parasitic capacitor of the second switch element SW2.
  • the reflux unit 14 is configured by the second switch element SW2, the setting of the reflux period can be appropriately performed by the on / off control of the second switch element SW2, and the switching of the second switch element SW2 by the zero voltage switching. Loss can be suppressed.
  • the configuration of the reflux unit 14 is not limited to this, and may be configured by, for example, one reflux diode.
  • the auxiliary resonant circuit 20 includes an auxiliary switch element SA and an auxiliary reactor LA, a first stabilizing diode (first diode) D21, and a second stabilizing diode (second diode) D22 connected in series.
  • the auxiliary resonance circuit 20 is connected to a first connection point N1 that is a connection point between the first switch element SW1 and the low-pass filter 13.
  • one end La1 of the auxiliary reactor LA of the auxiliary resonance circuit 20 is connected to the first connection point N1.
  • the other end La2 of the auxiliary reactor LA is connected to the drain D of the auxiliary switch element SA22.
  • the reactance of the auxiliary reactor LA is set to be sufficiently smaller than the smoothing reactor Lo.
  • the auxiliary switch element SA is controlled by the switch control unit 11 at the same time and is connected in series to two auxiliary switch elements SA (the first auxiliary switch element SA21 and the second auxiliary switch element SA21). It is constituted by an auxiliary switch element SA22).
  • Each auxiliary switch element SA21, SA22 is configured by an N-channel MOSFET in this embodiment.
  • the two auxiliary switch elements (SA21, SA22) are referred to as “auxiliary switch elements SA” when it is not necessary to distinguish between them.
  • the first stabilization diode D21 is connected between a second connection point N2 that is a connection point between the auxiliary reactor LA and the second auxiliary switch element SA22 and the ground line Lg. Specifically, the cathode of the first stabilization diode D21 is connected to the second connection point N2, and the anode of the first stabilization diode D21 is connected to the ground line Lg.
  • the second stabilization diode D22 is connected between the third connection point N3, which is an intermediate connection point between the two auxiliary switch elements SA21 and SA22, and the internal power supply line Ls. Specifically, the cathode of the second stabilization diode D22 is connected to the internal power supply line Ls, and the anode of the second stabilization diode D22 is connected to the third connection point N3.
  • the first stabilization diode D21 and the second stabilization diode D22 stabilize the voltage Vsa between the drain and the source of the auxiliary switch element SA when the auxiliary switch element SA is turned off.
  • the auxiliary voltage application unit 12 is electrically connected to the auxiliary resonance circuit 20 and the ground line Lg, and supplies the auxiliary voltage VA having a constant voltage lower than the voltage value of the input voltage Vin to the auxiliary reactor LA via the auxiliary switch element SA. Apply.
  • the auxiliary voltage application unit is configured by the battery 12 that outputs the auxiliary voltage VA. At that time, the positive electrode side output of the battery 12 is connected to the drain terminal of the first auxiliary switch element SA21 of the auxiliary resonance circuit 20, and the negative electrode side output of the battery 12 is connected to the ground line Lg.
  • the auxiliary voltage VA is not less than half of the input voltage Vin and less than the input voltage Vin.
  • the auxiliary voltage VA is about 30 V, for example.
  • the switch control unit 11 is connected to each switch element (SW1, SW2, SA), and generates a gate control signal (G1, G2, GA) for controlling on / off switching of each switch element. Specifically, the switch control unit 11 switches the first and second switch elements (SW1, SW2) by so-called zero voltage switching (ZVS) according to the gate control signals (G1, G2). The switch control unit 11 switches the auxiliary switch element SA by so-called zero current switching (ZCS) by the gate control signal GA.
  • Each switch element (SW1, SW2, SA) is not limited to an N-channel MOSFET. For example, an IGBT or the like may be used.
  • the auxiliary switch element SA is the gate control signal.
  • the GA that is, when zero current switching (ZCS) is performed, the resonance operation by the auxiliary resonance circuit 20 is started.
  • the resonance current Irs that is a current flowing through the auxiliary switch element SA and the auxiliary reactor LA is increased, and accordingly, the second current Isw2 that is a current flowing through the second switch element SW2 is decreased.
  • the increasing speed of the resonance current Irs depends on the reactance magnitude of the auxiliary reactor LA.
  • an output current Io that is a current flowing through the smoothing reactor Lo is constant. Note that the output current Io is substantially constant without being limited to the first period K1.
  • the second switch element SW2 is turned off. As the second switch element SW2 is turned off, the second current Isw2 further decreases and becomes zero at time t1.
  • FIG. 4 shows a current flow in a period (second period K2) from time t1 to time t2 when the first connection point voltage Vn1 becomes larger than the input voltage Vin.
  • the resonance current Irs mainly includes the first parallel capacitor C1 and the second parallel capacitor C2. (See currents Ic1 and Ic2 in FIG. 4).
  • the first parallel capacitor C1 is discharged, while the second parallel capacitor C2 is charged. Therefore, the first connection point voltage Vn1 increases.
  • the first connection point voltage Vn1 is equal to the second voltage Vsw2 which is the drain-source voltage of the second switch element SW2. Therefore, as shown in FIG. 2, the second voltage Vsw2 increases in the second period K2.
  • FIG. 5 shows a state from time t2 to time t3 (third period K3), which is a conduction period of the body diode D1. At this time, the first current Isw1 in the reverse direction flows through the body diode D1.
  • the first switch element SW1 is turned on while the body diode D1 is conducting (time t3). That is, the first switch element SW1 is zero voltage switched (ZVS). At this time, a reverse voltage (input voltage Vin ⁇ auxiliary voltage VA) is applied to the auxiliary reactor LA. Then, as shown in FIG. 2, after time t3, the first current Isw1, which is the current flowing through the first switch element SW1, increases, and the resonance current Irs decreases. Then, after the value of the first current Isw1 reaches the output current Io, the resonance current Irs becomes zero (time t4).
  • FIG. 6 shows a current flow in a period (fourth period K4) from time t3 to time t4.
  • the first current Isw1 in the reverse direction first flows through the body diode D1, but when the resonance current Irs decreases and becomes smaller than the output current Io, the first current Isw1 in the forward direction. Begins to flow.
  • FIG. 7 shows a current flow in a period (fifth period K5) from time t4 to time t5.
  • the second switch element SW2 is in the off state, and the auxiliary resonance circuit 20 is not operating, so that a normal conversion operation is performed.
  • the first current Isw1 is commutated to the first parallel capacitor C1 and the second parallel capacitor C2 (see currents Ic1 and Ic2 in FIG. 8).
  • the first connection point voltage Vn1 (second voltage Vsw2) drops rapidly.
  • the body diode D2 and the first stabilization diode D21 become conductive (see current Id21 in FIG. 9).
  • the first stabilization diode D21 is turned on, the potential at one end (second connection point N2) of the auxiliary reactor LA is maintained near zero V, and the oscillation of the potential at the second connection point N2 is suppressed.
  • FIG. 8 shows a current flow in a period (sixth period K6) from time t5 to time t6, which is the first half of the dead time
  • FIG. 9 shows from time t6 to time t7, which is the second half of the dead time. The flow of current in the period (seventh period K7) is shown.
  • the on / off timing of each gate control signal is determined by a known method. That is, the on / off timing is determined by the switch control unit 11 based on a comparison between a detection signal from a detection circuit (not shown) that detects an electrical quantity such as the resonance current Irs and a reference value, for example. Alternatively, it is determined in advance by calculation based on circuit constants such as the reactance value of the auxiliary reactor LA. In this case, the determined timing data is stored in a memory or the like of the switch control unit 11, and the switch control unit 11 determines the on / off timing based on the stored data. Alternatively, the on / off timing is determined based on both the detection signal and the stored data.
  • an auxiliary voltage application unit 12 that supplies power to the auxiliary resonance circuit 20 is provided. Therefore, the loss due to the auxiliary resonance circuit 20, for example, the switching loss due to the auxiliary switch elements (SA21, SA22) is not added to the switching loss of the first switch element SW1 when the input voltage Vin is converted to the output voltage Vout.
  • the first switch element SW1 and the second switch element SW2 are zero-voltage switched, and the auxiliary switch elements (SA21, SA22) are zero-current switched. Therefore, according to the direct-current voltage converter 10 of the first embodiment, high conversion efficiency can be maintained even when applied to a large-capacity load.
  • the first stabilization diode D21 connected between the second connection point N2 and the ground line Lg is provided.
  • the first stabilization diode D21 can stabilize the potential at the second connection point N2 during the period when the auxiliary switch element SA is off. That is, in the period when the auxiliary switch element SA21 is off and the second switch element SW2 is on (seventh period K7), when the N-channel MOSFET is used as the auxiliary switch element SA as in the first embodiment, the auxiliary switch element It is conceivable that the potential at the second connection point N2 fluctuates via the parasitic capacitance of SA, and the potential at the second connection point N2 rises more than the input voltage Vin. However, at that time, the fluctuation of the potential at the second connection point N2 is suppressed by the first stabilization diode D21. Note that the first stabilization diode D21 may be omitted.
  • the auxiliary switch element SA is composed of two auxiliary switch elements (SA21, SA22) that are connected in series and controlled simultaneously by the switch control unit 11. For this reason, the on-resistance as the auxiliary switch element SA increases. Accordingly, the on-current that flows when the auxiliary switch element SA is turned on is reduced, and the on-resistance loss of the auxiliary switch element SA is reduced as compared with the case where the number of the auxiliary switch element SA is one. That is, the loss (power) is proportional to the square of the current. In this case, the amount of decrease in the on-resistance loss due to the decrease in the on-current is greater than the amount of increase in the on-resistance loss associated with the increase in on-resistance. Therefore, on-resistance loss is reduced.
  • the second stabilization diode D22 connected between the third connection point N3, which is an intermediate connection point between the two auxiliary switch elements (SA21, SA2), and the internal power supply line Ls is provided. ing.
  • the second stabilization diode D22 can stabilize the potential at the third connection point N3 during the period in which the first auxiliary switch element (one auxiliary switch element) SA21 close to the auxiliary voltage applying unit 12 is off. That is, during the period when the first auxiliary switch element SA21 is off and the second auxiliary switch element (the other auxiliary switch element) SA22 and the second switch element SW2 are on, the first auxiliary switch element SA21 as in the first embodiment.
  • the potential of the third connection point N3 varies via the parasitic capacitance of the first auxiliary switch element SA21. At this time, the fluctuation of the potential at the third connection point N3 is suppressed by the second stabilization diode D22. Note that the second stabilization diode D22 may be omitted.
  • each switch element can be made substantially the same level as the input voltage Vin, and the current flowing through each switch element can be made almost the same level as the output current Io. Therefore, each switch element can be a component with a small rating, thereby reducing conduction loss.
  • the auxiliary voltage applying unit 12A in the second embodiment includes an external connection terminal J1 connected to the intermediate potential unit 40m of the battery 40 having a voltage value “VA”, an external connection terminal J1, and an auxiliary And a voltage application line Lv connecting the switch element SA21.
  • the voltage application line Lv is connected to the drain terminal of the first auxiliary switch element SA21 of the auxiliary resonance circuit 20, and the external connection terminal J1 is connected to the ground line Lg via the battery 40.
  • auxiliary voltage application unit 12A in the second embodiment it is not necessary to separately provide a configuration of an auxiliary power source such as a battery in the DC voltage converter 10, and the auxiliary voltage application unit can be formed with a simple configuration.
  • the configuration of the auxiliary voltage application unit is not limited to this.
  • a converter that converts the input voltage Vin into the auxiliary voltage VA may be provided, and the auxiliary voltage application unit 12 may be configured by this converter.
  • the battery 40 as the main power source may be provided as the configuration of the DC voltage conversion device 10 and the auxiliary voltage application unit may be configured by a part of the battery.
  • the auxiliary switch element SA is configured by two auxiliary switch elements (SA21, SA2), but is not limited thereto.
  • the auxiliary switch element SA may be configured by one auxiliary switch element SA21.
  • the reflux unit 14 is configured by the second switch element SW2 and the second parallel capacitor C2 is shown, but the present invention is not limited thereto.
  • the reflux unit 14 may be configured by a single reflux diode.
  • the DC voltage converter 10 is applied to a chopper type step-down DC-DC converter.
  • the DC voltage converter 10 is replaced with a chopper type boost DC-DC converter. It can also be applied to a DC converter.
  • FIG. 11 shows an example of control and operation when the DC voltage converter 10 is applied to a chopper type step-up DC-DC converter.
  • FIG. 11 shows an example of control and operation in the boost mode in a bidirectional step-down / step-up DC-DC converter in which the input side and the output side can be reversed.
  • the input side of the DC voltage converter 10 is connected to a 48V battery and the output side is connected to a 12V battery.
  • time t0 indicates the time when the gate control signal GA is turned on
  • time t1 indicates the time when the gate control signal G2 is turned off
  • time t2 indicates the time when the gate control signal G1 is turned on
  • Time t3 indicates the time when the gate control signal G1 is turned off
  • time t4 indicates the time when the gate control signal GA is turned off
  • time t5 indicates the time when the gate control signal G2 is turned on
  • Time t6 indicates the time when the gate control signal GA is turned on again.
  • the step-up mode can be realized with the same circuit configuration as that of the first embodiment shown in FIG. 1, and only the on / off timing of each gate control signal (G1, G2, GA) is different from that of the first embodiment.
  • the step-down DC-DC converter shown in FIG. 1 can be operated as a step-up DC-DC converter by changing only the on / off timing of each gate control signal (G1, G2, GA).
  • the output current Io increases as the ON time of the first switch element SW1 (the time from time t2 to time t3 in FIG. 11) is increased, and the output current Io decreases as the time is shortened.
  • the ON time of the first switch element SW1 at the time when the output current Io becomes zero is further shortened, the current of the DC voltage converter 10 starts to flow in the reverse direction (from the low voltage side to the high voltage side) and enters the boost mode. change. This means that the low pressure on the output side (right side in FIG. 1) has been converted to the high pressure on the input side (left side in FIG. 1).
  • the second switch element SW2 becomes a synchronous rectifier element at the time of step-down
  • the first switch element SW1 becomes a synchronous rectifier element at the time of step-up.
  • all the switch elements are zero-voltage or zero-current switching (soft switching).
  • the DC voltage conversion apparatus 10 is a bidirectional type by simply changing the on / off timing of each gate control signal (G1, G2, GA) without changing the circuit configuration.
  • the step-down / step-up DC-DC converter can be realized.
  • the DC voltage converter 10 is not limited to this, and can also be applied to a normal unidirectional step-up DC-DC converter in which the input side and the output side are fixed.
  • auxiliary switch element SA21 ... first auxiliary switch element (N-channel MOSFET) SA22: second auxiliary switch element (N-channel MOSFET) SW1... First switch element (N-channel MOSFET) SW2: Second switch element (N-channel MOSFET)

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Abstract

Selon l'invention, un dispositif (10) de conversion de tension continue comporte: un premier élément de commutation (SW1) connecté à une ligne électrique interne (Ls); un filtre passe-bas (13); un élément de commutation auxiliaire (SA) connecté en série; et un réacteur auxiliaire (LA). Le dispositif (10) comporte également un circuit résonnant auxiliaire (20) connecté à un premier point de connexion (N1), lequel est le point de connexion entre le premier élément de commutation (SW1) et le filtre passe-bas (13). En outre, ce dispositif (10) de conversion de tension continue comporte: une unité (12) d'application de tension, laquelle est connectée électriquement au circuit résonnant auxiliaire (20) et à une ligne de terre (Lg), et laquelle applique une tension auxiliaire (VA) fixe inférieure à la tension d'entrée (Vin) au réacteur auxiliaire (LA), par l'intermédiaire de l'élément de commutation auxiliaire (SA); et une unité de commande (11) de commutation, laquelle commute le premier élément de commutation (SW1) à une tension nulle et l'élément de commutation auxiliaire (SA) à un courant nul.
PCT/JP2018/005834 2017-03-07 2018-02-20 Dispositif de conversion de tension continue WO2018163792A1 (fr)

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JP2017-042871 2017-03-07
JP2017042871A JP2018148724A (ja) 2017-03-07 2017-03-07 直流電圧変換装置

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Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH06269165A (ja) * 1993-03-11 1994-09-22 Sanken Electric Co Ltd Ｐｗｍ型ｄｃ−ｄｃコンバータ
JP2002171759A (ja) * 2000-05-10 2002-06-14 Hitachi Medical Corp Ｄｃ−ｄｃコンバータ及びこれを用いたｘ線高電圧装置
JP2002252965A (ja) * 2001-02-22 2002-09-06 Denso Corp 補助共振転流回路を用いた電力変換装置

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH06269165A (ja) * 1993-03-11 1994-09-22 Sanken Electric Co Ltd Ｐｗｍ型ｄｃ−ｄｃコンバータ
JP2002171759A (ja) * 2000-05-10 2002-06-14 Hitachi Medical Corp Ｄｃ−ｄｃコンバータ及びこれを用いたｘ線高電圧装置
JP2002252965A (ja) * 2001-02-22 2002-09-06 Denso Corp 補助共振転流回路を用いた電力変換装置

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