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WO2013114573A1 - Load power source device - Google Patents

Load power source device Download PDF

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Publication number
WO2013114573A1
WO2013114573A1 PCT/JP2012/052173 JP2012052173W WO2013114573A1 WO 2013114573 A1 WO2013114573 A1 WO 2013114573A1 JP 2012052173 W JP2012052173 W JP 2012052173W WO 2013114573 A1 WO2013114573 A1 WO 2013114573A1
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WO
WIPO (PCT)
Prior art keywords
energy storage
storage source
energy
inductor
load power
Prior art date
Application number
PCT/JP2012/052173
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French (fr)
Japanese (ja)
Inventor
ミハエル フィッシャー
ヨハン エッカート
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本田技研工業株式会社
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
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Application filed by 本田技研工業株式会社 filed Critical 本田技研工業株式会社
Priority to DE201211005790 priority Critical patent/DE112012005790T5/en
Priority to PCT/JP2012/052173 priority patent/WO2013114573A1/en
Publication of WO2013114573A1 publication Critical patent/WO2013114573A1/en

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/02—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries for charging batteries from AC mains by converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J2207/00—Indexing scheme relating to details of circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J2207/20—Charging or discharging characterised by the power electronics converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0064—Magnetic structures combining different functions, e.g. storage, filtering or transformation

Definitions

  • the present invention relates to a load power supply that charges a second energy storage source that compensates for the output or capacity of the first energy storage source.
  • FIG. 7 is a configuration diagram showing the configuration of the battery power circuit disclosed in Patent Document 1.
  • the battery power circuit shown in FIG. 7 includes a battery 1 to which a load to which power is to be supplied is connected, a series connected power source in which a capacitor group 2 is connected in series with each other, between battery 1 and capacitor group 2, , DC / DC converter 3 for transferring power between battery 1 and load, and control device 5 for controlling DC / DC converter 3.
  • Control device 5 detects the voltage of capacitor group 2 If the detected voltage is smaller than the first threshold voltage (for example, 4.0 V), the DC / DC converter 3 charges the capacitor group 2. The total voltage of the battery 1 and the capacitor group 2 is applied to the power conversion circuit 4.
  • the first threshold voltage for example, 4.0 V
  • the control device 5 performs switching control of the MOSFET 31 as the upper arm switch or the MOSFET 32 as the lower arm switch, whereby the battery 1 and the capacitor Power transfer takes place between group two.
  • a current flows through the inductance 33, and the capacitor group 2 is charged and discharged.
  • the invention disclosed in Patent Document 1 is for a battery capable of preventing a decrease in power supplied to the motor at the time of start-up and obtaining a predetermined engine speed even when the idle stop operation is continuously performed.
  • the purpose is to obtain a power circuit. That is, when the voltage of the capacitor group 2 is smaller than the predetermined value, the engine rotation is maintained, and the capacitor group 2 is charged by the step-up operation of the DC / DC converter 3.
  • the present invention also applies to the output control of the DC / DC converter according to the capacitor voltage which falls with time when torque assist is performed to operate the motor simultaneously with the engine. Applied. In any case, it is desirable that the time required for charging the capacitor group 2 by the operation of the DC / DC converter 3 be short.
  • An object of the present invention is to provide a load power supply capable of shortening the time required for charging a second energy storage source to compensate for the output or capacity of the first energy storage source.
  • a load power supply device of the invention comprises a first energy storage source (for example, a battery Bat in the embodiment); A second energy storage source (e.g., a capacitor SC in the embodiment) serially connected to the energy storage source, and an inductor (between the first energy storage source and the second energy storage source)
  • a DC / DC converter for example, the DC / DC converter 105 in the embodiment
  • the inductance component on the path of the reactor current flowing through the first energy storage source or the second energy storage source causes the inductance component of the energy from the first energy storage source or the second energy storage source to Are being different from each accumulation time and upon release of the energy stored in the inductor to.
  • the DC / DC converter when energy is transferred from the second energy storage source to the first energy storage source, stores energy in the inductor.
  • a first switching element for example, the transistor T1 in the embodiment
  • a second switching element for example, the transistor T2 in the embodiment
  • the second switch is connected to the connection point of the second energy storage source, and the other end of the inductor is connected to the second switch. Is connected to one end of the grayed element, in the middle of the winding of the inductor, it is characterized in that one end of said first switching element is connected.
  • the first energy storage source and the second energy storage source are energy obtained by energy regeneration by a load to which the load power supply supplies electric power.
  • a switch for example, the switch 201 in the embodiment for selecting whether to charge both or either the first energy storage source or the second energy storage source. It is characterized.
  • the first energy storage source is disposed on the low voltage side
  • the second energy storage source is disposed on the high voltage side.
  • the time required to charge the second energy storage source that compensates for the output or capacity of the first energy storage source can be shortened.
  • the voltage obtained by energy regeneration is lower than the voltage required to charge both the first energy storage source and the second energy storage source. Also, any one of the first energy storage source and the second energy storage source can be charged.
  • FIG. 3 is a diagram showing the relationship between the internal configuration of the load power supply device of the first embodiment and the variable load and converter control device.
  • (A) and (b) is a figure which shows each state when the transistor T2 is turned on / off in the load power supply device shown in FIG. 1 with the transistor T1 turned off.
  • (A) And (b) is a graph which shows a time-dependent change of reactor current when transistor T2 is switching-controlled.
  • (A) and (b) is a figure which shows each state when the transistor T1 is turned on / off in the load power supply device shown in FIG. 1 with the transistor T2 turned off.
  • (A) And (b) is a graph which shows a time-dependent change of reactor current when transistor T1 is switching-controlled.
  • FIG. 1 is a diagram showing the relationship between the internal configuration of the load power supply device of the first embodiment and the variable load and the converter control device.
  • the load power supply device of the first embodiment is connected to a variable load 101 including a DC / AC inverter and a motor / generator.
  • the load power supply device includes a battery Bat, an electric double layer capacitor (hereinafter simply referred to as “capacitor”) SC, a variable inductor VI, transistors T1 and T2, and a free wheeling diode (hereinafter simply referred to as “diode”) D1. And D2.
  • the switching control to turn on and off the transistors T1 and T2 is performed by the converter control device 103.
  • variable inductor VI, the transistors T1 and T2, and the diodes D1 and D2 constitute a DC / DC converter 105 shown by a dotted line in FIG.
  • the DC / DC converter 105 charges and discharges energy between the battery Bat and the capacitor SC via the variable inductor VI.
  • An end point 1 and an end point 3 are provided at both ends of the winding of the variable inductor VI, and an end point 2 for utilizing a part of the inductance of the winding is also provided.
  • the end point 2 when the number of turns of the variable inductor VI is “N”, the end point 2 is provided at a position where the number of turns from the end point 1 is N / 2. Therefore, when the inductance of the variable inductor VI is “L”, the inductance from the end point 1 to the end point 2 is “L / 4”. The position of the end point 2 on the winding of the variable inductor VI is variable.
  • the output voltage of the battery Bat is a substantially constant DC voltage, which is higher than the maximum voltage that the capacitor SC can output.
  • the battery Bat and the capacitor SC are connected in series, and the terminal point 1 of the variable inductor VI is connected to the connection point.
  • the collector of the transistor T2 is connected to the end point 3 of the variable inductor VI, and the emitter of the transistor T1 is connected to the end point 2.
  • a diode D1 is connected in parallel to the transistor T1, and a diode D2 is connected in parallel to the transistor T2.
  • the cathode of the reflux diode is connected to the collector of the transistor, and the anode of the reflux diode is connected to the emitter of the transistor.
  • FIGS. 2 (a) and 2 (b), and FIGS. b) to explain.
  • FIGS. 2A and 2B are diagrams showing respective states when the transistor T2 is turned on and off while the transistor T1 is in the off state in the load power supply device shown in FIG. 2 (a) shows the reactor current IL when the transistor T2 is in the on state by a dotted line, and FIG. 2 (b) shows the reactor current when the transistor T2 is turned from the on state to the off state. IL is shown as a dotted line.
  • reactor current IL flows from the battery Bat to the transistor T2 via the end point 1 and the end point 3 of the variable inductor VI, as shown in FIG. At this time, energy from the battery Bat is stored in the variable inductor VI.
  • the transistor T2 is turned off, the energy stored in the variable inductor VI is released as shown in FIG. 2 (b). Therefore, the reactor current IL is transmitted through the end point 1 and the end point 2 of the variable inductor VI. It flows through the diode D1.
  • the energy stored in the variable inductor VI from the battery Bat in the state shown in FIG. 2A is transferred to the capacitor SC. That is, the energy of the battery Bat charges the capacitor SC.
  • FIGS. 3A and 3B are graphs showing time-dependent changes in reactor current when the transistor T2 is subjected to switching control.
  • FIG. 3 (a) shows the time-dependent change of the reactor current IL in the load power supply device of the first embodiment shown in FIG. 1
  • FIG. 3 (b) shows that the emitter of the transistor T1 is connected to the end point 3
  • the change over time of the reactor current IL in the load power supply device of the different configuration is shown.
  • the load power supply device having a configuration in which the emitter of the transistor T1 is connected to the end point 3 is the same as the configuration of the battery 1, capacitor group 2 and DC / DC converter 3 of the battery power circuit shown in FIG.
  • the load power supply device When the converter control device 103 turns on only the transistor T2 when both the transistors T1 and T2 are in the off state, the load power supply device according to the first embodiment is in the state shown in FIG. 2A, and FIG.
  • the reactor current IL is increased as shown in FIG.
  • Converter control device 103 turns on transistor T2, and when time tc1 elapses, returns the transistor T2 to the off state.
  • the time tc1 is expressed by the following equation (1).
  • Vbat is a voltage between terminals of the battery Bat.
  • tc1 L ⁇ ILth / Vbat (1)
  • the load power supply device of the first embodiment is in the state shown in FIG. 2 (b), and as shown in FIG. 3 (a), the reactor current IL decreases.
  • the reactor current IL in the state shown in FIG. 2A flows through the end point 1 and the end point 3 of the variable inductor VI
  • the inductance component on the path of the reactor current IL is “L”.
  • the reactor current IL in the state shown in FIG. 2B flows through the end point 1 and the end point 2 of the variable inductor VI
  • the inductance component on the path of the reactor current IL is “L / 4”.
  • the reactor current IL decreases from twice the value (2ILth) immediately before the off control.
  • Vsc is a voltage between terminals of the capacitor SC.
  • the time td1 is half of the time td1pa.
  • time T1 of one cycle in on / off control of the transistor T2 is shortened. For this reason, it is possible to shorten the time for charging the capacitor SC by the energy of the battery Bat.
  • FIGS. 4 (a) and 4 (b), and FIGS. Description will be made with reference to b).
  • FIGS. 4A and 4B are diagrams showing respective states when the transistor T1 is turned on and off while the transistor T2 is in the off state in the load power supply device shown in FIG. 4 (a) shows the reactor current IL when the transistor T1 is in the on state by a dotted line, and FIG. 4 (b) shows the reactor current when the transistor T1 is turned from the on state to the off state. IL is shown as a dotted line.
  • the reactor current IL flows from the capacitor SC to the end point 2 and the end point 1 of the variable inductor VI via the transistor T1, as shown in FIG. At this time, energy from the capacitor SC is stored in the variable inductor VI.
  • the transistor T1 is turned off, the energy stored in the variable inductor VI is released as shown in FIG. 4B, so that the reactor current IL passes through the end point 1 and the end point 3 of the variable inductor VI. It flows through the diode D2.
  • the energy stored in the variable inductor VI from the capacitor SC is transferred to the battery Bat. That is, the energy of the capacitor SC charges the battery Bat.
  • FIGS. 5A and 5B are graphs showing time-dependent changes in reactor current when the transistor T1 is subjected to switching control.
  • FIG. 5 (a) shows the time-dependent change of the reactor current IL in the load power supply device of the first embodiment shown in FIG. 1
  • FIG. 5 (b) shows that the emitter of the transistor T1 is connected to the end point 3.
  • the time-dependent change of reactor current IL in the load power supply device of the same composition as conventional is shown.
  • the load power supply device of the first embodiment is in the state shown in FIG. 4 (b), and as shown in FIG. 5 (a) It decreases from the value of (ILth).
  • a time td2 until the variable inductor VI finishes releasing energy and the reactor current IL becomes 0 is expressed by the following equation (5).
  • the inductance component on the path of the reactor current IL is "L / 4" .
  • the inductance component on the path of the reactor current IL is “L”.
  • the inductance component on the path of the reactor current IL is “L” both when the transistor T1 is in the on state and in the off state. It remains unchanged.
  • the time tc2 is half of the time tc2pa.
  • time T2 of one cycle in on / off control of the transistor T1 is shortened. Therefore, the time for charging the battery Bat with the energy of the capacitor SC can be shortened.
  • the end point 2 of the variable inductor VI is provided at a position where the number of turns from the end point 1 is N / 2, ie, at a midpoint, For example, it is not limited to the middle point.
  • the end point 2 may be provided at a position where the number of turns from the end point 1 is N / 3.
  • the time for charging the capacitor SC by the energy of the battery Bat can be further shortened.
  • FIG. 6 is a diagram showing the relationship between the internal configuration of the load power supply device of the second embodiment and the variable load and the converter control device.
  • the difference between the load power supply device of the second embodiment and the load power supply device of the first embodiment is that a switch 201 is provided.
  • the second embodiment is the same as the first embodiment, and in FIG. 6, the same or equivalent parts as the components of the first embodiment are given the same reference numerals or corresponding reference numerals to simplify or omit the description.
  • the switch 201 connects the negative terminal of the variable load to either the terminal n1 connected to the emitter of the transistor T1 (anode of the diode D1) or the terminal n2 connected to the emitter of the transistor T2 (anode of the diode D2). Do.
  • the switch 201 is controlled by the converter control device 103.
  • Converter control device 103 controls switch 201 based on the magnitude of voltage (hereinafter referred to as “regenerative voltage”) Vrg generated when variable load 101 performs a regenerative operation.
  • the regenerative voltage Vrg is detected by the voltage sensor 203 shown in FIG.
  • the converter control device 103 of the present embodiment selects the terminal n2 of the switch 201 if the regenerative voltage Vrg is a predetermined value or more, and selects the terminal n1 of the switch 201 if the regenerative voltage Vrg is less than the predetermined value.
  • the predetermined value is a voltage required to charge the capacitor SC and the battery Bat.
  • the electric path in which the terminal n2 is selected is the same as the electric path shown in FIG. 1 in the first embodiment, and the regenerative voltage Vrg charges the capacitor SC and the battery Bat.
  • the regenerative voltage Vrg when the terminal n1 is selected charges only the capacitor SC.
  • the regenerative voltage Vrg generated when the brake operation is performed at a low vehicle speed, that is, when the rotation speed of the motor / generator is low is low.
  • the low regenerative voltage Vrg is not sufficient for charging the capacitor SC and the battery Bat, but in the present embodiment, the low regenerative voltage Vrg is applied only to the capacitor SC.
  • the regenerative energy generated at low vehicle speeds can be used effectively.
  • the transistors T1 and T2 are used as switching elements, but semiconductor elements such as MOSFETs and IGBTs may be used as switching elements.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

A load power source device is provided with: a first energy storage source; a second energy storage source connected in series to the first energy storage source; and a DC/DC converter for converting energy via an inductor between the first energy storage source and the second energy storage source. The inductance component on the path of the reactor current flowing through the inductor varies between when the inductor is storing energy from the first energy storage source or second energy storage source and when the energy stored in the inductor is being released. Thus, it is possible to reduce the time needed to charge the second energy storage source, which supplements the output or capacity of the first energy storage source.

Description

負荷電源装置Load power supply
　本発明は、第１のエネルギー蓄積源の出力又は容量を補う第２のエネルギー蓄積源を充電する負荷電源装置に関する。 The present invention relates to a load power supply that charges a second energy storage source that compensates for the output or capacity of the first energy storage source.
　図７は、特許文献１に開示されたバッテリ用電力回路の構成を示した構成図である。図７に示すバッテリ用電力回路は、電力供給対象である負荷が接続されるバッテリ１と、コンデンサ群２とを互いに直列に接続した直列接続電源と、バッテリ１とコンデンサ群２との間、および、バッテリ１と負荷との間で電力を移行させるためのＤＣ／ＤＣコンバータ３と、ＤＣ／ＤＣコンバータ３の制御を行う制御装置５とを備え、制御装置５は、コンデンサ群２の電圧を検知し、検知した電圧が第１の閾値電圧（例えば、４．０Ｖ）より小さい場合はＤＣ／ＤＣコンバータ３により、コンデンサ群２への充電を行う。電力変換回路４には、バッテリ１とコンデンサ群２の合計電圧が印加される。 FIG. 7 is a configuration diagram showing the configuration of the battery power circuit disclosed in Patent Document 1. As shown in FIG. The battery power circuit shown in FIG. 7 includes a battery 1 to which a load to which power is to be supplied is connected, a series connected power source in which a capacitor group 2 is connected in series with each other, between battery 1 and capacitor group 2, , DC / DC converter 3 for transferring power between battery 1 and load, and control device 5 for controlling DC / DC converter 3. Control device 5 detects the voltage of capacitor group 2 If the detected voltage is smaller than the first threshold voltage (for example, 4.0 V), the DC / DC converter 3 charges the capacitor group 2. The total voltage of the battery 1 and the capacitor group 2 is applied to the power conversion circuit 4.
国際公開第２００４／０６６４７２号（図１）WO 2004/066472 (Figure 1)
　特許文献１に開示されたバッテリ用電力回路に含まれるＤＣ／ＤＣコンバータ３では、上アームスイッチとしてのＭＯＳＦＥＴ３１又は下アームスイッチとしてのＭＯＳＦＥＴ３２が制御装置５によってスイッチング制御されることで、バッテリ１とコンデンサ群２の間で電力伝送が行われる。バッテリ１とコンデンサ群２の間で電力伝送が行われる際、インダクタンス３３には電流が流れ、コンデンサ群２は充放電される。 In the DC / DC converter 3 included in the battery power circuit disclosed in Patent Document 1, the control device 5 performs switching control of the MOSFET 31 as the upper arm switch or the MOSFET 32 as the lower arm switch, whereby the battery 1 and the capacitor Power transfer takes place between group two. When power transmission is performed between the battery 1 and the capacitor group 2, a current flows through the inductance 33, and the capacitor group 2 is charged and discharged.
　なお、特許文献１に開示された発明は、連続してアイドルストップ動作を行った場合でも、始動時のモータへの供給電力の低下を防止し、所定のエンジン回転数を得ることができるバッテリ用電力回路を得ることを目的としている。すなわち、コンデンサ群２の電圧が所定値より小さい場合は、エンジン回転を維持し、ＤＣ／ＤＣコンバータ３の昇圧動作によりコンデンサ群２を充電する。また、特許文献１で説明されているように、当該発明は、エンジンと共にモータも同時に動作させるトルクアシストが行われるとき、経時的に降下するコンデンサ電圧に応じたＤＣ／ＤＣコンバータの出力制御にも適用される。いずれの場合であっても、ＤＣ／ＤＣコンバータ３の動作によるコンデンサ群２の充電に要する時間は短い方が望ましい。 The invention disclosed in Patent Document 1 is for a battery capable of preventing a decrease in power supplied to the motor at the time of start-up and obtaining a predetermined engine speed even when the idle stop operation is continuously performed. The purpose is to obtain a power circuit. That is, when the voltage of the capacitor group 2 is smaller than the predetermined value, the engine rotation is maintained, and the capacitor group 2 is charged by the step-up operation of the DC / DC converter 3. Further, as described in Patent Document 1, the present invention also applies to the output control of the DC / DC converter according to the capacitor voltage which falls with time when torque assist is performed to operate the motor simultaneously with the engine. Applied. In any case, it is desirable that the time required for charging the capacitor group 2 by the operation of the DC / DC converter 3 be short.
　本発明の目的は、第１のエネルギー蓄積源の出力又は容量を補う第２のエネルギー蓄積源の充電に要する時間を短縮可能な負荷電源装置を提供することである。 An object of the present invention is to provide a load power supply capable of shortening the time required for charging a second energy storage source to compensate for the output or capacity of the first energy storage source.
　上記課題を解決して係る目的を達成するために、請求項１に記載の発明の負荷電源装置は、第１のエネルギー蓄積源（例えば、実施の形態でのバッテリＢａｔ）と、前記第１のエネルギー蓄積源に直列に接続された第２のエネルギー蓄積源（例えば、実施の形態でのキャパシタＳＣ）と、前記第１のエネルギー蓄積源と前記第２のエネルギー蓄積源との間で、インダクタ（例えば、実施の形態での可変インダクタＶＩ）を介してエネルギーを交換するＤＣ／ＤＣコンバータ（例えば、実施の形態でのＤＣ／ＤＣコンバータ１０５）と、を備えた負荷電源装置であって、前記インダクタを流れるリアクトル電流の経路上のインダクタンス成分が、前記第１のエネルギー蓄積源又は前記第２のエネルギー蓄積源からのエネルギーの前記インダクタへの蓄積時と前記インダクタに蓄積されたエネルギーの放出時とでそれぞれ異なることを特徴としている。 In order to solve the above problems and achieve the object, a load power supply device of the invention according to claim 1 comprises a first energy storage source (for example, a battery Bat in the embodiment); A second energy storage source (e.g., a capacitor SC in the embodiment) serially connected to the energy storage source, and an inductor (between the first energy storage source and the second energy storage source) For example, a DC / DC converter (for example, the DC / DC converter 105 in the embodiment) exchanging energy via the variable inductor VI in the embodiment (for example, the load power supply device), The inductance component on the path of the reactor current flowing through the first energy storage source or the second energy storage source causes the inductance component of the energy from the first energy storage source or the second energy storage source to Are being different from each accumulation time and upon release of the energy stored in the inductor to.
　さらに、請求項２に記載の発明の負荷電源装置では、前記ＤＣ／ＤＣコンバータは、前記第２のエネルギー蓄積源から前記第１のエネルギー蓄積源にエネルギーを移行するとき、前記インダクタにおけるエネルギーの蓄積と放出に対応してオンオフされる第１のスイッチング素子（例えば、実施の形態でのトランジスタＴ１）と、前記第１のエネルギー蓄積源から前記第２のエネルギー蓄積源にエネルギーを移行するとき、前記インダクタにおけるエネルギーの蓄積と放出に対応してオンオフされる第２のスイッチング素子（例えば、実施の形態でのトランジスタＴ２）と、を有し、前記インダクタの一端は、前記第１のエネルギー蓄積源と前記第２のエネルギー蓄積源の接続点に接続され、前記インダクタの他端は、前記第２のスイッチング素子の一端に接続され、前記インダクタの巻線の途中に、前記第１のスイッチング素子の一端が接続されたことを特徴としている。 Furthermore, in the load power supply device of the invention according to claim 2, when energy is transferred from the second energy storage source to the first energy storage source, the DC / DC converter stores energy in the inductor. And a first switching element (for example, the transistor T1 in the embodiment) which is turned on / off in response to the emission, and when energy is transferred from the first energy storage source to the second energy storage source, And a second switching element (for example, the transistor T2 in the embodiment) which is turned on / off in response to storage and release of energy in the inductor, one end of the inductor being the first energy storage source and The second switch is connected to the connection point of the second energy storage source, and the other end of the inductor is connected to the second switch. Is connected to one end of the grayed element, in the middle of the winding of the inductor, it is characterized in that one end of said first switching element is connected.
　さらに、請求項３に記載の発明の負荷電源装置では、当該負荷電源装置が電力を供給する負荷によるエネルギー回生で得られたエネルギーを、前記第１のエネルギー蓄積源及び前記第２のエネルギー蓄積源の両方に充電するか、前記第１のエネルギー蓄積源及び前記第２のエネルギー蓄積源のいずれか一方に充電するかを選択するスイッチ（例えば、実施の形態でのスイッチ２０１）を備えたことを特徴としている。 Furthermore, in the load power supply device of the invention according to claim 3, the first energy storage source and the second energy storage source are energy obtained by energy regeneration by a load to which the load power supply supplies electric power. Having a switch (for example, the switch 201 in the embodiment) for selecting whether to charge both or either the first energy storage source or the second energy storage source. It is characterized.
　さらに、請求項４に記載の発明の負荷電源装置では、前記第１のエネルギー蓄積源は低電圧側に配置され、前記第２のエネルギー蓄積源は高電圧側に配置されたことを特徴としている。 Furthermore, in the load power supply device of the invention according to claim 4, the first energy storage source is disposed on the low voltage side, and the second energy storage source is disposed on the high voltage side. .
　請求項１～４に記載の発明の負荷電源装置によれば、第１のエネルギー蓄積源の出力又は容量を補う第２のエネルギー蓄積源の充電に要する時間を短縮できる。 According to the load power supply device of the present invention, the time required to charge the second energy storage source that compensates for the output or capacity of the first energy storage source can be shortened.
　請求項３に記載の発明の負荷電源装置によれば、エネルギー回生で得られる電圧が前記第１のエネルギー蓄積源及び前記第２のエネルギー蓄積源の両方を充電するために必要な電圧より低くても、前記第１のエネルギー蓄積源及び前記第２のエネルギー蓄積源のいずれか一方を充電することができる。 According to the load power supply device of the third aspect of the present invention, the voltage obtained by energy regeneration is lower than the voltage required to charge both the first energy storage source and the second energy storage source. Also, any one of the first energy storage source and the second energy storage source can be charged.
第１の実施形態の負荷電源装置の内部構成と可変負荷及びコンバータ制御装置との関係を示す図FIG. 3 is a diagram showing the relationship between the internal configuration of the load power supply device of the first embodiment and the variable load and converter control device. （ａ）及び（ｂ）は、図１に示した負荷電源装置において、トランジスタＴ１はオフ状態のまま、トランジスタＴ２をオンオフした時の各状態を示す図(A) and (b) is a figure which shows each state when the transistor T2 is turned on / off in the load power supply device shown in FIG. 1 with the transistor T1 turned off. （ａ）及び（ｂ）は、トランジスタＴ２がスイッチング制御されたときのリアクトル電流の経時変化を示すグラフ(A) And (b) is a graph which shows a time-dependent change of reactor current when transistor T2 is switching-controlled. （ａ）及び（ｂ）は、図１に示した負荷電源装置において、トランジスタＴ２はオフ状態のまま、トランジスタＴ１をオンオフした時の各状態を示す図(A) and (b) is a figure which shows each state when the transistor T1 is turned on / off in the load power supply device shown in FIG. 1 with the transistor T2 turned off. （ａ）及び（ｂ）は、トランジスタＴ１がスイッチング制御されたときのリアクトル電流の経時変化を示すグラフ(A) And (b) is a graph which shows a time-dependent change of reactor current when transistor T1 is switching-controlled. 第２の実施形態の負荷電源装置の内部構成と可変負荷及びコンバータ制御装置との関係を示す図The figure which shows the relationship between the internal structure of the load power supply device of 2nd Embodiment, a variable load, and a converter control apparatus. 特許文献１に開示されたバッテリ用電力回路の構成を示した構成図The block diagram which showed the structure of the battery power circuit disclosed by patent document 1
　以下、本発明の実施形態について、図面を参照して説明する。 Hereinafter, embodiments of the present invention will be described with reference to the drawings.
（第１の実施形態）
　図１は、第１の実施形態の負荷電源装置の内部構成と可変負荷及びコンバータ制御装置との関係を示す図である。図１に示すように、第１の実施形態の負荷電源装置は、ＤＣ／ＡＣインバータ及びモータ／ジェネレータ等を含む可変負荷１０１に接続される。当該負荷電源装置は、バッテリＢａｔと、電気二重層キャパシタ（以下、単に「キャパシタ」という）ＳＣと、可変インダクタＶＩと、トランジスタＴ１，Ｔ２と、還流ダイオード（以下、単に「ダイオード」という）Ｄ１，Ｄ２とを備える。なお、トランジスタＴ１，Ｔ２をオンオフするスイッチング制御は、コンバータ制御装置１０３によって行われる。また、可変インダクタＶＩ、トランジスタＴ１，Ｔ２及びダイオードＤ１，Ｄ２は、図１に点線で示すＤＣ／ＤＣコンバータ１０５を構成する。ＤＣ／ＤＣコンバータ１０５は、バッテリＢａｔとキャパシタＳＣとの間で、可変インダクタＶＩを介してエネルギーを充放電する。 First Embodiment
FIG. 1 is a diagram showing the relationship between the internal configuration of the load power supply device of the first embodiment and the variable load and the converter control device. As shown in FIG. 1, the load power supply device of the first embodiment is connected to a variable load 101 including a DC / AC inverter and a motor / generator. The load power supply device includes a battery Bat, an electric double layer capacitor (hereinafter simply referred to as “capacitor”) SC, a variable inductor VI, transistors T1 and T2, and a free wheeling diode (hereinafter simply referred to as “diode”) D1. And D2. The switching control to turn on and off the transistors T1 and T2 is performed by the converter control device 103. The variable inductor VI, the transistors T1 and T2, and the diodes D1 and D2 constitute a DC / DC converter 105 shown by a dotted line in FIG. The DC / DC converter 105 charges and discharges energy between the battery Bat and the capacitor SC via the variable inductor VI.
　可変インダクタＶＩの巻線の両端には端点１と端点３が設けられ、当該巻線のインダクタンスの一部を利用するための端点２も設けられる。本実施形態では、可変インダクタＶＩの巻線数を「Ｎ」としたとき、端点１からの巻線数がＮ／２の位置に端点２が設けられている。したがって、可変インダクタＶＩのインダクタンスを「Ｌ」としたとき、端点１から端点２のインダクタンスは「Ｌ／４」である。なお、可変インダクタＶＩの巻線上における端点２の位置は可変である。 An end point 1 and an end point 3 are provided at both ends of the winding of the variable inductor VI, and an end point 2 for utilizing a part of the inductance of the winding is also provided. In the present embodiment, when the number of turns of the variable inductor VI is “N”, the end point 2 is provided at a position where the number of turns from the end point 1 is N / 2. Therefore, when the inductance of the variable inductor VI is “L”, the inductance from the end point 1 to the end point 2 is “L / 4”. The position of the end point 2 on the winding of the variable inductor VI is variable.
　バッテリＢａｔの出力電圧は、略一定した直流電圧であり、キャパシタＳＣが出力可能な最大電圧よりも高い。バッテリＢａｔとキャパシタＳＣは直列に接続されており、その接続点に可変インダクタＶＩの端点１が接続されている。また、可変インダクタＶＩの端点３にはトランジスタＴ２のコレクタが接続され、端点２にはトランジスタＴ１のエミッタが接続されている。また、トランジスタＴ１にはダイオードＤ１が並列に接続され、トランジスタＴ２にはダイオードＤ２が並列に接続されている。なお、トランジスタのコレクタには還流ダイオードのカソードが接続され、トランジスタのエミッタには還流ダイオードのアノードが接続されている。 The output voltage of the battery Bat is a substantially constant DC voltage, which is higher than the maximum voltage that the capacitor SC can output. The battery Bat and the capacitor SC are connected in series, and the terminal point 1 of the variable inductor VI is connected to the connection point. Further, the collector of the transistor T2 is connected to the end point 3 of the variable inductor VI, and the emitter of the transistor T1 is connected to the end point 2. Further, a diode D1 is connected in parallel to the transistor T1, and a diode D2 is connected in parallel to the transistor T2. The cathode of the reflux diode is connected to the collector of the transistor, and the anode of the reflux diode is connected to the emitter of the transistor.
　以下、バッテリＢａｔのエネルギーによってキャパシタＳＣが充電されるときの状態及びこのとき可変インダクタＶＩを流れるリアクトル電流ＩＬの変化について、図２（ａ）及び（ｂ）、並びに、図３（ａ）及び（ｂ）を参照して説明する。 Hereinafter, with respect to the state when the capacitor SC is charged by the energy of the battery Bat and the change of the reactor current IL flowing through the variable inductor VI at this time, FIGS. 2 (a) and 2 (b), and FIGS. b) to explain.
　図２（ａ）及び（ｂ）は、図１に示した負荷電源装置において、トランジスタＴ１はオフ状態のまま、トランジスタＴ２をオンオフした時の各状態を示す図である。なお、図２（ａ）には、トランジスタＴ２がオン状態のときのリアクトル電流ＩＬが点線で示され、図２（ｂ）には、トランジスタＴ２がオン状態からオフ状態になったときのリアクトル電流ＩＬが点線で示される。 FIGS. 2A and 2B are diagrams showing respective states when the transistor T2 is turned on and off while the transistor T1 is in the off state in the load power supply device shown in FIG. 2 (a) shows the reactor current IL when the transistor T2 is in the on state by a dotted line, and FIG. 2 (b) shows the reactor current when the transistor T2 is turned from the on state to the off state. IL is shown as a dotted line.
　トランジスタＴ１をオフ状態のまま、トランジスタＴ２をオンすると、図２（ａ）に示すように、バッテリＢａｔから可変インダクタＶＩの端点１及び端点３を介してトランジスタＴ２にリアクトル電流ＩＬが流れ出す。このとき、可変インダクタＶＩにはバッテリＢａｔからのエネルギーが蓄積される。次に、トランジスタＴ２をオフすると、図２（ｂ）に示すように、可変インダクタＶＩに蓄積されたエネルギーが放出されるため、リアクトル電流ＩＬが、可変インダクタＶＩの端点１及び端点２を介してダイオードＤ１を流れる。このとき、図２（ａ）に示した状態のときバッテリＢａｔから可変インダクタＶＩに蓄えられたエネルギーが、キャパシタＳＣに移る。すなわち、バッテリＢａｔのエネルギーによってキャパシタＳＣが充電される。 When the transistor T2 is turned on while the transistor T1 is in the off state, reactor current IL flows from the battery Bat to the transistor T2 via the end point 1 and the end point 3 of the variable inductor VI, as shown in FIG. At this time, energy from the battery Bat is stored in the variable inductor VI. Next, when the transistor T2 is turned off, the energy stored in the variable inductor VI is released as shown in FIG. 2 (b). Therefore, the reactor current IL is transmitted through the end point 1 and the end point 2 of the variable inductor VI. It flows through the diode D1. At this time, the energy stored in the variable inductor VI from the battery Bat in the state shown in FIG. 2A is transferred to the capacitor SC. That is, the energy of the battery Bat charges the capacitor SC.
　図３（ａ）及び（ｂ）は、トランジスタＴ２がスイッチング制御されたときのリアクトル電流の経時変化を示すグラフである。但し、図３（ａ）は、図１に示した第１の実施形態の負荷電源装置におけるリアクトル電流ＩＬの経時変化を示し、図３（ｂ）は、トランジスタＴ１のエミッタが端点３に接続された構成の負荷電源装置におけるリアクトル電流ＩＬの経時変化を示す。なお、トランジスタＴ１のエミッタが端点３に接続された構成の負荷電源装置は、図７に示したバッテリ用電力回路のバッテリ１とコンデンサ群２とＤＣ／ＤＣコンバータ３の構成と同じである。 FIGS. 3A and 3B are graphs showing time-dependent changes in reactor current when the transistor T2 is subjected to switching control. However, FIG. 3 (a) shows the time-dependent change of the reactor current IL in the load power supply device of the first embodiment shown in FIG. 1, and FIG. 3 (b) shows that the emitter of the transistor T1 is connected to the end point 3 The change over time of the reactor current IL in the load power supply device of the different configuration is shown. The load power supply device having a configuration in which the emitter of the transistor T1 is connected to the end point 3 is the same as the configuration of the battery 1, capacitor group 2 and DC / DC converter 3 of the battery power circuit shown in FIG.
　トランジスタＴ１，Ｔ２が共にオフの状態のとき、コンバータ制御装置１０３がトランジスタＴ２だけをオンすると、第１の実施形態の負荷電源装置は図２（ａ）に示した状態となり、図３（ａ）に示すように、リアクトル電流ＩＬが増加する。コンバータ制御装置１０３は、トランジスタＴ２をオンして時間ｔｃ１が経過した時点で、トランジスタＴ２をオフ状態に戻す。なお、時間ｔｃ１は、以下の式（１）によって表される。なお、ＶｂａｔはバッテリＢａｔの端子間電圧である。
　ｔｃ１＝Ｌ×ＩＬｔｈ／Ｖｂａｔ　…（１） When the converter control device 103 turns on only the transistor T2 when both the transistors T1 and T2 are in the off state, the load power supply device according to the first embodiment is in the state shown in FIG. 2A, and FIG. The reactor current IL is increased as shown in FIG. Converter control device 103 turns on transistor T2, and when time tc1 elapses, returns the transistor T2 to the off state. The time tc1 is expressed by the following equation (1). Vbat is a voltage between terminals of the battery Bat.
tc1 = L × ILth / Vbat (1)
　トランジスタＴ２がオン状態からオフ制御されると、第１の実施形態の負荷電源装置は図２（ｂ）に示した状態となり、図３（ａ）に示すように、リアクトル電流ＩＬが減少する。上述したように、図２（ａ）に示した状態のリアクトル電流ＩＬは可変インダクタＶＩの端点１と端点３を流れるため、当該リアクトル電流ＩＬの経路上のインダクタンス成分は「Ｌ」である。一方、図２（ｂ）に示した状態のリアクトル電流ＩＬは可変インダクタＶＩの端点１と端点２を流れるため、当該リアクトル電流ＩＬの経路上のインダクタンス成分は「Ｌ／４」である。その結果、トランジスタＴ２がオン状態からオフ制御されると、図３（ａ）に示すように、リアクトル電流ＩＬはオフ制御される直前の２倍の値（２ＩＬｔｈ）から減少していく。 When the transistor T2 is controlled from the on state to the off state, the load power supply device of the first embodiment is in the state shown in FIG. 2 (b), and as shown in FIG. 3 (a), the reactor current IL decreases. As described above, since the reactor current IL in the state shown in FIG. 2A flows through the end point 1 and the end point 3 of the variable inductor VI, the inductance component on the path of the reactor current IL is “L”. On the other hand, since the reactor current IL in the state shown in FIG. 2B flows through the end point 1 and the end point 2 of the variable inductor VI, the inductance component on the path of the reactor current IL is “L / 4”. As a result, when the transistor T2 is controlled from the on state to the off state, as shown in FIG. 3A, the reactor current IL decreases from twice the value (2ILth) immediately before the off control.
　このとき、可変インダクタＶＩがエネルギーを放出し終わってリアクトル電流ＩＬが０になるまでの時間ｔｄ１は、以下の式（２）によって表される。なお、ＶｓｃはキャパシタＳＣの端子間電圧である。
　ｔｄ１＝（Ｌ／４）×２ＩＬｔｈ／Ｖｓｃ
　　　　＝Ｌ×ＩＬｔｈ／２Ｖｓｃ　…（２） At this time, a time td1 until the variable inductor VI finishes releasing energy and the reactor current IL becomes 0 is expressed by the following equation (2). Vsc is a voltage between terminals of the capacitor SC.
td1 = (L / 4) × 2 ILth / Vsc
= L x ILth / 2 Vsc (2)
　一方、トランジスタＴ１のエミッタが端点３に接続された従来の構成の負荷電源装置であると、リアクトル電流ＩＬの経路上のインダクタンス成分は、トランジスタＴ２がオン状態のときもオフ状態のときも「Ｌ」のまま変わらない。その結果、トランジスタＴ２がオン状態からオフ状態に制御されると、図３（ｂ）に示すように、リアクトル電流ＩＬはオフ制御される直前の値（ＩＬｔｈ）から減少していく。このとき、インダクタがエネルギーを放出し終わってリアクトル電流ＩＬが０になるまでの時間ｔｄ１ｐａは、以下の式（３）によって表される。
　ｔｄ１ｐａ＝Ｌ×ＩＬｔｈ／Ｖｓｃ
　　　　　　＝Ｌ×ＩＬｔｈ／Ｖｓｃ　…（３） On the other hand, in the load power supply device of the conventional configuration in which the emitter of the transistor T1 is connected to the end point 3, the inductance component on the path of the reactor current IL is "L" both when the transistor T2 is on and off. It remains unchanged. As a result, when the transistor T2 is controlled from the on state to the off state, as shown in FIG. 3 (b), the reactor current IL decreases from the value (ILth) immediately before the off control. At this time, a time td1pa from when the inductor finishes releasing energy until the reactor current IL becomes 0 is expressed by the following equation (3).
td1pa = L × ILth / Vsc
= L x ILth / Vsc (3)
　式（２）と式（３）から明らかなように、時間ｔｄ１は、時間ｔｄ１ｐａの半分の時間である。その結果、図３（ａ）及び（ｂ）に示すように、トランジスタＴ２のオンオフ制御における１サイクルの時間Ｔ１が短縮される。このため、バッテリＢａｔのエネルギーによってキャパシタＳＣを充電するときの時間を短縮できる。 As apparent from the equations (2) and (3), the time td1 is half of the time td1pa. As a result, as shown in FIGS. 3A and 3B, time T1 of one cycle in on / off control of the transistor T2 is shortened. For this reason, it is possible to shorten the time for charging the capacitor SC by the energy of the battery Bat.
　以下、キャパシタＳＣのエネルギーによってバッテリＢａｔが充電されるときの状態及びこのとき可変インダクタＶＩを流れるリアクトル電流ＩＬの変化について、図４（ａ）及び（ｂ）、並びに、図５（ａ）及び（ｂ）を参照して説明する。 Hereinafter, with respect to the state when the battery Bat is charged by the energy of the capacitor SC and the change of the reactor current IL flowing through the variable inductor VI at this time, FIGS. 4 (a) and 4 (b), and FIGS. Description will be made with reference to b).
　図４（ａ）及び（ｂ）は、図１に示した負荷電源装置において、トランジスタＴ２はオフ状態のまま、トランジスタＴ１をオンオフした時の各状態を示す図である。なお、図４（ａ）には、トランジスタＴ１がオン状態のときのリアクトル電流ＩＬが点線で示され、図４（ｂ）には、トランジスタＴ１がオン状態からオフ状態になったときのリアクトル電流ＩＬが点線で示される。 FIGS. 4A and 4B are diagrams showing respective states when the transistor T1 is turned on and off while the transistor T2 is in the off state in the load power supply device shown in FIG. 4 (a) shows the reactor current IL when the transistor T1 is in the on state by a dotted line, and FIG. 4 (b) shows the reactor current when the transistor T1 is turned from the on state to the off state. IL is shown as a dotted line.
　トランジスタＴ２をオフ状態のまま、トランジスタＴ１をオンすると、図４（ａ）に示すように、キャパシタＳＣからトランジスタＴ１を介して可変インダクタＶＩの端点２及び端点１にリアクトル電流ＩＬが流れ出す。このとき、可変インダクタＶＩにはキャパシタＳＣからのエネルギーが蓄積される。次に、トランジスタＴ１をオフすると、図４（ｂ）に示すように、可変インダクタＶＩに蓄積されたエネルギーが放出されるため、リアクトル電流ＩＬが、可変インダクタＶＩの端点１及び端点３を介してダイオードＤ２を流れる。このとき、図４（ａ）に示した状態のときキャパシタＳＣから可変インダクタＶＩに蓄えられたエネルギーが、バッテリＢａｔに移る。すなわち、キャパシタＳＣのエネルギーによってバッテリＢａｔが充電される。 When the transistor T1 is turned on while the transistor T2 is in the off state, the reactor current IL flows from the capacitor SC to the end point 2 and the end point 1 of the variable inductor VI via the transistor T1, as shown in FIG. At this time, energy from the capacitor SC is stored in the variable inductor VI. Next, when the transistor T1 is turned off, the energy stored in the variable inductor VI is released as shown in FIG. 4B, so that the reactor current IL passes through the end point 1 and the end point 3 of the variable inductor VI. It flows through the diode D2. At this time, in the state shown in FIG. 4A, the energy stored in the variable inductor VI from the capacitor SC is transferred to the battery Bat. That is, the energy of the capacitor SC charges the battery Bat.
　図５（ａ）及び（ｂ）は、トランジスタＴ１がスイッチング制御されたときのリアクトル電流の経時変化を示すグラフである。但し、図５（ａ）は、図１に示した第１の実施形態の負荷電源装置におけるリアクトル電流ＩＬの経時変化を示し、図５（ｂ）は、トランジスタＴ１のエミッタが端点３に接続された従来と同じ構成の負荷電源装置におけるリアクトル電流ＩＬの経時変化を示す。 FIGS. 5A and 5B are graphs showing time-dependent changes in reactor current when the transistor T1 is subjected to switching control. However, FIG. 5 (a) shows the time-dependent change of the reactor current IL in the load power supply device of the first embodiment shown in FIG. 1, and FIG. 5 (b) shows that the emitter of the transistor T1 is connected to the end point 3. The time-dependent change of reactor current IL in the load power supply device of the same composition as conventional is shown.
　トランジスタＴ１，Ｔ２が共にオフの状態のとき、コンバータ制御装置１０３がトランジスタＴ１だけをオンすると、第１の実施形態の負荷電源装置は図４（ａ）に示した状態となり、可変インダクタＶＩがエネルギーを蓄積して、図５（ａ）に示すようにリアクトル電流ＩＬが増加する。コンバータ制御装置１０３は、トランジスタＴ１をオンして時間ｔｃ２が経過した時点で、トランジスタＴ１をオフ状態に戻す。なお、時間ｔｃ２は、以下の式（４）によって表される。
　ｔｃ２＝（Ｌ／４）×２ＩＬｔｈ／Ｖｓｃ
　　　　＝Ｌ×ＩＬｔｈ／２Ｖｓｃ　…（４） When the converter control device 103 turns on only the transistor T1 while both the transistors T1 and T2 are in the off state, the load power supply device of the first embodiment is in the state shown in FIG. To increase the reactor current IL as shown in FIG. 5 (a). Converter control device 103 turns on transistor T1, and when time tc2 elapses, returns the transistor T1 to the off state. The time tc2 is represented by the following equation (4).
tc2 = (L / 4) × 2 ILth / Vsc
= L x ILth / 2 Vsc (4)
　トランジスタＴ１がオン状態からオフ制御されると、第１の実施形態の負荷電源装置は図４（ｂ）に示した状態となり、図５（ａ）に示すように、オフ制御される直前の半分の値（ＩＬｔｈ）から減少していく。このとき、可変インダクタＶＩがエネルギーを放出し終わってリアクトル電流ＩＬが０になるまでの時間ｔｄ２は、以下の式（５）によって表される。
　ｔｄ２＝Ｌ×ＩＬｔｈ／Ｖｂａｔ…（５） When the transistor T1 is controlled from the on state to the off state, the load power supply device of the first embodiment is in the state shown in FIG. 4 (b), and as shown in FIG. 5 (a) It decreases from the value of (ILth). At this time, a time td2 until the variable inductor VI finishes releasing energy and the reactor current IL becomes 0 is expressed by the following equation (5).
td2 = L × ILth / Vbat (5)
　上述したように、図４（ａ）に示した状態のリアクトル電流ＩＬは可変インダクタＶＩの端点２と端点１を流れるため、当該リアクトル電流ＩＬの経路上のインダクタンス成分は「Ｌ／４」である。また、図４（ｂ）に示した状態のリアクトル電流ＩＬは可変インダクタＶＩの端点３と端点１を流れるため、当該リアクトル電流ＩＬの経路上のインダクタンス成分は「Ｌ」である。一方、トランジスタＴ１のエミッタが端点３に接続された従来の構成の負荷電源装置であると、リアクトル電流ＩＬの経路上のインダクタンス成分は、トランジスタＴ１がオン状態のときもオフ状態のときも「Ｌ」のまま変わらない。このため、トランジスタＴ１がオフ状態からオン状態に制御されると、図５（ｂ）に示すように、リアクトル電流ＩＬの増加率は小さい。なお、インダクタがエネルギーを蓄積してリアクトル電流ＩＬがＩＬｔｈになるまでの時間ｔｃ２ｐａは、以下の式（６）によって表される。
　ｔｃ２ｐａ＝Ｌ×ＩＬｔｈ／Ｖｓｃ
　　　　　　＝Ｌ×ＩＬｔｈ／Ｖｓｃ　…（６） As described above, since the reactor current IL in the state shown in FIG. 4A flows through the end point 2 and the end point 1 of the variable inductor VI, the inductance component on the path of the reactor current IL is "L / 4" . Further, since the reactor current IL in the state shown in FIG. 4B flows through the end point 3 and the end point 1 of the variable inductor VI, the inductance component on the path of the reactor current IL is “L”. On the other hand, in the load power supply device of the conventional configuration in which the emitter of the transistor T1 is connected to the end point 3, the inductance component on the path of the reactor current IL is “L” both when the transistor T1 is in the on state and in the off state. It remains unchanged. For this reason, when the transistor T1 is controlled from the off state to the on state, the increase rate of the reactor current IL is small as shown in FIG. 5 (b). In addition, time tc2pa until an inductor accumulates energy and reactor current IL becomes ILth is represented by the following formula (6).
tc2pa = L × ILth / Vsc
= L x ILth / Vsc (6)
　式（４）と式（６）から明らかなように、時間ｔｃ２は、時間ｔｃ２ｐａの半分の時間である。その結果、図５（ａ）及び（ｂ）に示すように、トランジスタＴ１のオンオフ制御における１サイクルの時間Ｔ２が短縮される。このため、キャパシタＳＣのエネルギーによってバッテリＢａｔを充電するときの時間を短縮できる。 As apparent from the equations (4) and (6), the time tc2 is half of the time tc2pa. As a result, as shown in FIGS. 5A and 5B, time T2 of one cycle in on / off control of the transistor T1 is shortened. Therefore, the time for charging the battery Bat with the energy of the capacitor SC can be shortened.
　なお、本実施形態では、可変インダクタＶＩの端点２が、端点１からの巻線数がＮ／２の位置、すなわち中点（midpoint）に設けられているが、巻線の途中の位置であれば中点に限らない。例えば、端点２が、端点１からの巻線数がＮ／３の位置に設けられていても良い。このとき、トランジスタＴ２がオン状態からオフ制御された時点からリアクトル電流ＩＬが０になるまでの時間ｔｄ１は、以下の式（２Ａ）によって表される。
　ｔｄ１＝（Ｌ／９）×３ＩＬｔｈ／Ｖｓｃ
　　　　＝Ｌ×ＩＬｔｈ／３Ｖｓｃ　…（２Ａ）
　このとき、バッテリＢａｔのエネルギーによってキャパシタＳＣを充電するときの時間をさらに短縮できる。 In the present embodiment, although the end point 2 of the variable inductor VI is provided at a position where the number of turns from the end point 1 is N / 2, ie, at a midpoint, For example, it is not limited to the middle point. For example, the end point 2 may be provided at a position where the number of turns from the end point 1 is N / 3. At this time, a time td1 from when the transistor T2 is controlled from the on state to the off state until the reactor current IL becomes 0 is expressed by the following equation (2A).
td1 = (L / 9) × 3 ILth / Vsc
= L x ILth / 3 Vsc ... (2A)
At this time, the time for charging the capacitor SC by the energy of the battery Bat can be further shortened.
　また、トランジスタＴ１がオフ状態からオン制御されて、リアクトル電流ＩＬが３ＩＬｔｈに到達して再びトランジスタＴ１がオフ制御されるまでの時間ｔｃ２は、以下の式（４Ａ）によって表される。
　ｔｃ２＝（Ｌ／９）×３ＩＬｔｈ／Ｖｓｃ
　　　　＝Ｌ×ＩＬｔｈ／３Ｖｓｃ　…（４Ａ）
　このとき、キャパシタＳＣのエネルギーによってバッテリＢａｔを充電するときの時間をさらに短縮できる。 Further, a time tc2 from when the transistor T1 is turned on to being turned on to turn on the reactor current IL to 3ILth and then turned off again is expressed by the following equation (4A).
tc2 = (L / 9) × 3 ILth / Vsc
= L x ILth / 3 Vsc ... (4A)
At this time, it is possible to further shorten the time for charging the battery Bat with the energy of the capacitor SC.
（第２の実施形態）
　図６は、第２の実施形態の負荷電源装置の内部構成と可変負荷及びコンバータ制御装置との関係を示す図である。第２の実施形態の負荷電源装置が第１の実施形態の負荷電源装置と異なる点は、スイッチ２０１を備えたことである。この点以外は第１の実施形態と同様であり、図６において、第１実施形態の構成要素と同一又は同等部分には同一符号又は相当符号を付して説明を簡略化又は省略する。 Second Embodiment
FIG. 6 is a diagram showing the relationship between the internal configuration of the load power supply device of the second embodiment and the variable load and the converter control device. The difference between the load power supply device of the second embodiment and the load power supply device of the first embodiment is that a switch 201 is provided. Except this point, the second embodiment is the same as the first embodiment, and in FIG. 6, the same or equivalent parts as the components of the first embodiment are given the same reference numerals or corresponding reference numerals to simplify or omit the description.
　スイッチ２０１は、可変負荷のマイナス側端子を、トランジスタＴ１のエミッタ（ダイオードＤ１のアノード）に接続された端子ｎ１及びトランジスタＴ２のエミッタ（ダイオードＤ２のアノード）に接続された端子ｎ２のいずれかに接続する。なお、スイッチ２０１は、コンバータ制御装置１０３によって制御される。コンバータ制御装置１０３は、可変負荷１０１が回生動作した際に発生する電圧（以下「回生電圧」という）Ｖｒｇの大きさに基づいて、スイッチ２０１を制御する。なお、回生電圧Ｖｒｇは、図６に示した電圧センサー２０３が検出する。 The switch 201 connects the negative terminal of the variable load to either the terminal n1 connected to the emitter of the transistor T1 (anode of the diode D1) or the terminal n2 connected to the emitter of the transistor T2 (anode of the diode D2). Do. The switch 201 is controlled by the converter control device 103. Converter control device 103 controls switch 201 based on the magnitude of voltage (hereinafter referred to as “regenerative voltage”) Vrg generated when variable load 101 performs a regenerative operation. The regenerative voltage Vrg is detected by the voltage sensor 203 shown in FIG.
　本実施形態のコンバータ制御装置１０３は、回生電圧Ｖｒｇが所定値以上であればスイッチ２０１の端子ｎ２を選択し、所定値未満であればスイッチ２０１の端子ｎ１を選択する。なお、所定値は、キャパシタＳＣとバッテリＢａｔを充電するために必要な電圧である。端子ｎ２が選択された電気経路は第１の実施形態における図１に示した電気経路と同じであり、回生電圧Ｖｒｇは、キャパシタＳＣとバッテリＢａｔを充電する。一方、端子ｎ１が選択されたときの回生電圧Ｖｒｇは、キャパシタＳＣのみを充電する。 The converter control device 103 of the present embodiment selects the terminal n2 of the switch 201 if the regenerative voltage Vrg is a predetermined value or more, and selects the terminal n1 of the switch 201 if the regenerative voltage Vrg is less than the predetermined value. The predetermined value is a voltage required to charge the capacitor SC and the battery Bat. The electric path in which the terminal n2 is selected is the same as the electric path shown in FIG. 1 in the first embodiment, and the regenerative voltage Vrg charges the capacitor SC and the battery Bat. On the other hand, the regenerative voltage Vrg when the terminal n1 is selected charges only the capacitor SC.
　可変負荷１０１を構成するモータ／ジェネレータが車両の駆動源として用いられている場合、低車速、すなわちモータ／ジェネレータの回転数が低い状態でブレーキ操作が行われたときに発生する回生電圧Ｖｒｇは低い。低い回生電圧ＶｒｇはキャパシタＳＣとバッテリＢａｔの充電には十分ではないが、本実施形態では、低い回生電圧ＶｒｇはキャパシタＳＣにのみ印加される。このように、低車速時に発生した回生エネルギーを有効利用することができる。 When the motor / generator constituting the variable load 101 is used as a drive source of a vehicle, the regenerative voltage Vrg generated when the brake operation is performed at a low vehicle speed, that is, when the rotation speed of the motor / generator is low is low. . The low regenerative voltage Vrg is not sufficient for charging the capacitor SC and the battery Bat, but in the present embodiment, the low regenerative voltage Vrg is applied only to the capacitor SC. Thus, the regenerative energy generated at low vehicle speeds can be used effectively.
　上記説明した第１及び第２の実施形態では、スイッチング素子としてトランジスタＴ１，Ｔ２が用いられているが、ＭＯＳＦＥＴやＩＧＢＴ等の半導体素子をスイッチング素子として用いても良い。 In the first and second embodiments described above, the transistors T1 and T2 are used as switching elements, but semiconductor elements such as MOSFETs and IGBTs may be used as switching elements.
Ｂａｔ　バッテリ
ＳＣ　電気二重層キャパシタ（キャパシタ）
ＶＩ　可変インダクタ
Ｔ１，Ｔ２　トランジスタ
Ｄ１，Ｄ２　還流ダイオード（ダイオード）
１０１　可変負荷
１０３　コンバータ制御装置
１０５　ＤＣ／ＤＣコンバータ
２０１　スイッチ
２０３　電圧センサー Bat battery SC electric double layer capacitor (capacitor)
VI Variable Inductors T1, T2 Transistors D1, D2 Freewheeling Diode (Diode)
101 Variable Load 103 Converter Controller 105 DC / DC Converter 201 Switch 203 Voltage Sensor

Claims (4)

  1. 　第１のエネルギー蓄積源と、
    　前記第１のエネルギー蓄積源に直列に接続された第２のエネルギー蓄積源と、
    　前記第１のエネルギー蓄積源と前記第２のエネルギー蓄積源との間で、インダクタを介してエネルギーを交換するＤＣ／ＤＣコンバータと、を備えた負荷電源装置であって、
    　前記インダクタを流れるリアクトル電流の経路上のインダクタンス成分が、前記第１のエネルギー蓄積源又は前記第２のエネルギー蓄積源からのエネルギーの前記インダクタへの蓄積時と前記インダクタに蓄積されたエネルギーの放出時とでそれぞれ異なることを特徴とする負荷電源装置。     A first energy storage source,
    A second energy storage source connected in series to the first energy storage source;
    A DC / DC converter that exchanges energy between the first energy storage source and the second energy storage source via an inductor,
    An inductance component on a path of a reactor current flowing through the inductor stores energy from the first energy storage source or the second energy storage source into the inductor and releases energy stored in the inductor. And load power supply devices characterized by being different from each other.
  2. 　請求項１に記載の負荷電源装置であって、
    　前記ＤＣ／ＤＣコンバータは、
    　前記第２のエネルギー蓄積源から前記第１のエネルギー蓄積源にエネルギーを移行するとき、前記インダクタにおけるエネルギーの蓄積と放出に対応してオンオフされる第１のスイッチング素子と、
    　前記第１のエネルギー蓄積源から前記第２のエネルギー蓄積源にエネルギーを移行するとき、前記インダクタにおけるエネルギーの蓄積と放出に対応してオンオフされる第２のスイッチング素子と、を有し、
    　前記インダクタの一端は、前記第１のエネルギー蓄積源と前記第２のエネルギー蓄積源の接続点に接続され、
    　前記インダクタの他端は、前記第２のスイッチング素子の一端に接続され、
    　前記インダクタの巻線の途中に、前記第１のスイッチング素子の一端が接続されたことを特徴とする負荷電源装置。     The load power supply device according to claim 1, wherein
    The DC / DC converter is
    A first switching element that is turned on and off in response to storage and release of energy in the inductor when energy is transferred from the second energy storage source to the first energy storage source;
    A second switching element that is turned on / off in response to storage and release of energy in the inductor when energy is transferred from the first energy storage source to the second energy storage source;
    One end of the inductor is connected to a connection point of the first energy storage source and the second energy storage source,
    The other end of the inductor is connected to one end of the second switching element,
    One end of the first switching element is connected in the middle of the winding of the inductor.
  3. 　請求項１又は２に記載の負荷電源装置であって、
    　当該負荷電源装置が電力を供給する負荷によるエネルギー回生で得られたエネルギーを、前記第１のエネルギー蓄積源及び前記第２のエネルギー蓄積源の両方に充電するか、前記第１のエネルギー蓄積源及び前記第２のエネルギー蓄積源のいずれか一方に充電するかを選択するスイッチを備えたことを特徴とする負荷電源装置。     The load power supply device according to claim 1 or 2, wherein
    The energy obtained by energy regeneration by a load to which the load power supply apparatus supplies electric power is charged to both the first energy storage source and the second energy storage source, or the first energy storage source and A load power supply device comprising: a switch for selecting which one of the second energy storage sources is to be charged.
  4. 　請求項１～３のいずれか一項に記載の負荷電源装置であって、
    　前記第１のエネルギー蓄積源は低電圧側に配置され、前記第２のエネルギー蓄積源は高電圧側に配置されたことを特徴とする負荷電源装置。     The load power supply device according to any one of claims 1 to 3, wherein
    The load power supply device according to claim 1, wherein the first energy storage source is disposed on the low voltage side, and the second energy storage source is disposed on the high voltage side.
PCT/JP2012/052173 2012-01-31 2012-01-31 Load power source device WO2013114573A1 (en)

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CN103501036A (en) * 2013-10-28 2014-01-08 上海同异动力科技有限公司 Charging and discharging control circuit for lithium battery
CN116979659A (en) * 2023-06-20 2023-10-31 浙江华宇钠电新能源科技有限公司 Sodium ion battery and electric vehicle

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JP2003339165A (en) * 2002-05-17 2003-11-28 Cosel Co Ltd Synchronous rectification type switching power supply
WO2004066472A1 (en) * 2003-01-24 2004-08-05 Mitsubishi Denki Kabushiki Kaisha Battery power circuit

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JP2003339165A (en) * 2002-05-17 2003-11-28 Cosel Co Ltd Synchronous rectification type switching power supply
WO2004066472A1 (en) * 2003-01-24 2004-08-05 Mitsubishi Denki Kabushiki Kaisha Battery power circuit

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN103501036A (en) * 2013-10-28 2014-01-08 上海同异动力科技有限公司 Charging and discharging control circuit for lithium battery
CN116979659A (en) * 2023-06-20 2023-10-31 浙江华宇钠电新能源科技有限公司 Sodium ion battery and electric vehicle
CN116979659B (en) * 2023-06-20 2024-02-27 浙江华宇钠电新能源科技有限公司 Sodium ion battery and electric vehicle

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