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WO2009136368A1 - Convertisseur continu-continu à pompage de charge - Google Patents

Convertisseur continu-continu à pompage de charge Download PDF

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Publication number
WO2009136368A1
WO2009136368A1 PCT/IB2009/051851 IB2009051851W WO2009136368A1 WO 2009136368 A1 WO2009136368 A1 WO 2009136368A1 IB 2009051851 W IB2009051851 W IB 2009051851W WO 2009136368 A1 WO2009136368 A1 WO 2009136368A1
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WO
WIPO (PCT)
Prior art keywords
capacitors
node
voltage
converter
output
Prior art date
Application number
PCT/IB2009/051851
Other languages
English (en)
Inventor
Robert Jan Fronen
Original Assignee
Nxp B.V.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Nxp B.V. filed Critical Nxp B.V.
Publication of WO2009136368A1 publication Critical patent/WO2009136368A1/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/06—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using resistors or capacitors, e.g. potential divider
    • H02M3/07—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps

Definitions

  • the invention relates to an electronic circuit comprising a capacitive voltage converter.
  • DC-to-DC voltage converters are typically used in battery-operated electronic devices that have several circuits requiring different voltage levels. Also, a DC-to-DC converter is used to stabilize voltage supplied to a circuit, e.g., a light emitting diode (LED) circuit. Battery voltage decreases over time as the stored power is drained in operational use, whereas the circuit needs a more-or-less constant voltage supply.
  • a circuit e.g., a light emitting diode (LED) circuit.
  • LED light emitting diode
  • An example of a DC-to-DC converter is a switched-capacitor (SC) converter, also referred to as a "charge pump converter".
  • SC switched-capacitor
  • An SC converter alternately connects multiple capacitors to the input in a first configuration (e.g., connected in series) for being charged and to the output in another configuration (e.g., connected in parallel) for being discharged.
  • SC converter examples of an SC converter are given in, e.g., US patent 5,581,454; US patent 6,281,705; and US patent 6,657,875, all incorporated herein by reference.
  • the inventor has had the insight that the efficiency of the SC converter can be improved by means of using another configuration in the secondary cycles. This applies especially when the conversion factor between the input voltage and the output voltage lies between, e.g., 0.5 and 1.5.
  • the inventor therefore proposes an electronic device comprising an electronic circuit with a capacitive voltage converter.
  • the converter comprises an input node for receiving an input voltage; an output node for supplying an output voltage; a reference node for receiving a reference voltage (also referred to as "ground”); a plurality of capacitors; and switching means.
  • the switching means is configured for, in a first mode, connecting the capacitors in series between the input node and the reference node and, in a second mode, connecting the capacitors in parallel between the input node and the output node.
  • the invention is based on the insight that the input voltage source at the input node delivers the current to the buffer capacitance at the output node, if the parallel configuration of the capacitors is connected between the input node and the output node.
  • the capacitors themselves do not have to provide the majority of the electric energy to the buffer capacitance, as the energy is directly transferred from input to output.
  • Charging and discharging of a capacitor dissipates power through Ohmic losses and electromagnetic radiation.
  • the voltage source supplies the charging current to the buffer capacitance, the amount of charge involved in charging and discharging the capacitors is limited. This, in turn, increases the efficiency of the converter.
  • the device comprises an electronic circuit with a capacitive voltage converter.
  • the converter comprises: an input node for receiving an input voltage; an output node for supplying an output voltage; a reference node for receiving a reference voltage; a plurality of capacitors; and switching means.
  • the switching means is configured for, in a first mode, connecting the capacitors in series between the output node and the reference node and, in a second mode, connecting the capacitors in parallel between the input node and the output node.
  • the series configuration is now connected to the output node instead of to the input node in the embodiment first-mentioned. Both embodiments are variations on the same theme and provide a voltage conversion by a factor of (1 + n/k).
  • the switching means is preferably controlled so as to alternately implement the series configuration of the capacitors and the parallel configuration of the capacitors, using a certain controller that opens and closes the switches in different time slots with a certain frequency.
  • the invention also relates to a capacitive voltage converter configured for use in above devices.
  • the invention further relates to a method of converting an input voltage at an input node to an output voltage at an output node, using a plurality of capacitors and a reference node.
  • One embodiment of the method comprises: in a time slot connecting the capacitors in series between the input node and the reference node, and in another time slot connecting the capacitors in parallel between the input node and the output node.
  • Another embodiment of the method comprises: in a time slot connecting the capacitors in series between the output node and the reference node, and in another time slot connecting the capacitors in parallel between the input node and the output node.
  • Fig.1 is a circuit diagram illustrating the charging of a capacitor
  • Figs.2 and 3 give formulae explaining the operation of the circuit of Fig.l
  • Fig.4 is a diagram of a known capacitive voltage converter
  • Fig.5 is a diagram for explaining operation of the known converter during the secondary stroke
  • Fig.6 gives formulae for explaining operation of the known converter
  • Fig.7 is a circuit diagram of a converter in the invention
  • Fig.8 is a diagram for explaining operation of the converter in the invention during the secondary stroke
  • Fig.9 gives formulae for explaining operation of the converter in the invention.
  • Figs. 10 and 11 are diagrams of a converter in the invention that uses the series and parallel configurations in a manner opposite to that of the converter of Fig.7;
  • Fig.12 gives formulae explaining the converter of Figs.10 and 11.
  • LEDs Light emitting diodes
  • the high- brightness white LED is an LED system replacing the conventional Xenon flash.
  • One of the drawbacks of an LED-based lighting system is that the LED requires a stabilized supply current at low forward voltage of a few volts with large spread per device and halfway in between normal battery voltages. Therefore, powering an LED from a Li- ion battery in a highly efficient manner requires a voltage converter that is capable of converting voltage up or down depending on: the charge-condition of the battery, the output current and the forward voltage of the LED.
  • the invention relates, among other things, to a novel way of converting an input voltage to an output voltage only a small step up or down from the input voltage.
  • the invention relates to a capacitive converter.
  • a capacitive converter needs to be capable of generating an output voltage V ou t by means of making small steps around the input voltage V 1n :
  • V ou t (1 ⁇ k/n) V 1n , wherein "n” is an integer taking the value of, e.g., 4, 5 or 6, and wherein "k” is an integer ranging from, e.g., 1 to 4.
  • the inventor proposes a manner to make the small step down with lower losses and, therefore, with higher efficiency.
  • Fig.l is a diagram of a simple circuit 100 for illustrating the operation of charging a capacitor in terms of energies.
  • Circuit 100 comprises a constant voltage source 102 supplying a voltage V 1n .
  • Source 102 is connected to a series arrangement of a resistor 104 (having a resistance value R) and a capacitor 106 (having a capacitance value C) via a switch 108.
  • the initial condition is that switch 108 is not conducting, and that capacitor 106 is completely discharged.
  • switch 108 When switch 108 is conducting, source 102 supplies a current I(t) that decreases from a maximum value to zero when capacitor 106 is charged completely.
  • the time-integral of current I(t) represents the charge Q(t) stored at capacitor 106.
  • charge Q(t) does not increase anymore, the final stage has been reached wherein current I(t) has decreased to zero and the voltage across capacitor 106 equals supply voltage V 1n .
  • the energy supplied by source 102 is then given by expression (202).
  • the energy stored in capacitor 106 is given by expression (204).
  • the energy dissipated in resistor 104 is given by expression (206).
  • Current I as a function of time t is given by expression (208) with Io - V in /R.
  • Combining expression (208) with expression (206) gives expression (210). Accordingly, half of the energy supplied by source 102 in the process of charging capacitor 106 from completely empty to completely full is dissipated in resistor 104.
  • expressions (202) and (204) have been derived without mentioning resistor 104 at all. Accordingly, the discrepancy between the supplied energy from source 102 and the energy stored in capacitor 106 is independent of the resistance value of resistor 106.
  • Expression (212) gives an expression for the efficiency ⁇ of the process of charging capacitor 106 from completely empty to completely full. Using expressions (202) and (204) the efficiency ⁇ of above scenario is given as 0.5.
  • the charging of capacitor 106 was from completely empty to completely full.
  • the energy supplied by source 102 is given by expression (302).
  • the energy received by capacitor 106 is given by expression (304).
  • the efficiency ⁇ is now given by expression (306).
  • the efficiency ⁇ increases with a decreasing value of the quantity ⁇ V. Accordingly, it is advisable to keep the level of discharging of the capacitors, i.e., the magnitude of the quantity ⁇ V in an SC converter, as low as possible in order to maximize the efficiency.
  • Fig.4 is a diagram of an electronic device 400 comprising an electronic circuit with a known capacitive voltage converter 402.
  • Converter 402 comprises an input node 404 for receiving an input voltage from voltage source 102; an output node 406 for supplying an output voltage; and a reference node 408 for receiving a reference voltage, here ground.
  • Converter 402 further comprises a plurality of capacitors 410, 412, 414 and 416. In this example, capacitors 410-416 are assumed to have the same capacitance value.
  • Converter 402 also comprises controllable switching means implemented by switches 418, 420, 422, 424, 426, 428, 430, 432, 434, 436 and 438.
  • a first phase only switches 418, 426, 432 and 438 are conducting and the other switches are blocking.
  • capacitors 410-416 are connected in series between input node 404 and reference node 408.
  • switches 420, 426, 432, 434 and 436 are conducting.
  • capacitors 414 and 416 are connected in parallel between node 408 and a series connection of capacitors 410 and 412.
  • the series connection of capacitors 410 and 412 is also connected to output node 406.
  • only switches 422, 424, 428, 430, 434 and 436 are conducting.
  • Converter 400 further comprises a buffer capacitor 440 at output node 406.
  • Buffer capacitor 440 has a capacitance value much larger than the capacitance value of any individual one of capacitors 410-416. This condition keeps the output voltage at node 406 substantially constant per cycle of the three phases, mentioned above, in operational use of converter 102.
  • switches 418, 426, 432 and 438 are closed.
  • Capacitors 410-416 are then connected in series and each is charged to a voltage of A V 1n . This follows from the fact that, when the currents have ceased to flow, there is no net electric charge present in an imaginary box enclosing the lower plate of capacitor 410 and the upper plate of capacitor 412.
  • switches 420, 426, 432, 434 and 436 are closed, making a circuit of two capacitors in parallel connected in series with the other two. A voltage of 3 A V 1n is transferred to output 406.
  • the equalization stroke In the third phase, also referred to as the "equalization stroke", the differences in charge on the capacitors are equalized as a preparation for the next primary stroke.
  • the equalization stroke connects capacitors 410, 412, 414 and 416 in parallel. This equalization stroke is needed because the charges at series capacitors 410 and 412 and the charges at parallel capacitors 414 and 416 are unequal at the end of the secondary phase. Without equalization, the voltages at a node interconnecting two of capacitors 410- 416 is floating and drifts to levels that are uncontrolled and that can potentially damage the capacitors. Also note that the use of the equalization phase increases the time needed to run a full operational cycle, thus lowering, in effect, the frequency of operation.
  • capacitors 410-416 are discharged while displacing a charge Q according to expression (602) in Fig.6, wherein the quantity f is the frequency of the operational cycle of converter 402, and wherein the quantity ⁇ V is the voltage drop across connected capacitors 410-416 during discharge (also referred to as: "ripple voltage").
  • the ripple voltage is an important parameter.
  • the ripple voltage is associated with the current I out to output 408 according to expression (602), and hence with the output power E out according to expression (604) and output voltage V 0 Ut according to expression (606).
  • the ripple voltage is also associated with the losses Ei oss during the secondary stroke according to expression (608). Equation (606) indicates that converter 402 generates in principle a slightly lower output voltage V 0 Ut than in the ideal case due to the finite value of C.
  • capacitors 410-416 are connected in parallel so as to balance the energy by means of forcing an equal voltage across them according to expression (610). A small amount of energy is lost in the equalization stroke as given by expression (612).
  • capacitors 410-416 are primed for charging using the input voltage source in the primary stroke.
  • Capacitors 410-416 are then connected in series between node 404 carrying a voltage V 1n and reference node 408.
  • capacitors 410-416 are charged to a voltage of V 1n - 6/5 ⁇ V.
  • Capacitors 410-416 then store a total energy as given by expression (614).
  • capacitors 410-416 are each charged to a voltage of A V 1n .
  • the energy stored in capacitors 410-416 at the end of the primary stroke is given by expression (616).
  • the amount of energy extracted from the source providing input voltage V 1n is then given by expression (618).
  • Fig.7 is a circuit diagram of an electronic device 700 comprising an electronic circuit with a capacitive voltage converter 702 according to the invention.
  • Device 700 comprises, e.g., a battery-operated electronic device such as a mobile telephone, a mobile media player (e.g., a mobile MP3 player or a mobile video player, or a portable device equipped with an LED flash light.
  • Converter 702 comprises an input node 404 for receiving an input voltage from a voltage source (not shown); an output node 406 for supplying an output voltage; and a node 408 for receiving a reference voltage, here ground.
  • Converter 102 further comprises a plurality of capacitors 410, 412, 414 and 416.
  • Converter 702 also comprises controllable switching means implemented by first switches 718, 720, 722 and 724, and second switches 726, 728, 730, 732, 734, 736 and 738.
  • switches 718-724 are conducting and switches 726-738 are blocking.
  • capacitors 410-416 are connected in series between input node 404 and node 408.
  • switches 718-724 are blocking and switches 726-738 are conducting.
  • capacitors 410-416 are connected in parallel between input node 404 and output node 406.
  • the switching means is controlled so as to have capacitors 410-416 alternately in the series configuration and in the parallel configuration in cycles with a pre-determined duration.
  • a buffer capacitor 440 at output node 406 has a capacitance value much larger than the capacitance value of any individual one of capacitors 410- 416. This condition keeps the output voltage at node 406 substantially constant per cycle in operational use of converter 702.
  • Device 700 operates as follows. Instead of the three phases discussed with reference to device 400 of Fig.4, device 700 operates with only two phases: the primary stroke and the secondary stroke.
  • the primary stroke in device 700 is similar to the one discussed with regard to device 400.
  • capacitors 410- 416 are charged each to a voltage of A V 1n .
  • a voltage of magnitude: V 1n minus the voltage across any of capacitors 410-416 is transferred to output 406, resulting in a voltage at node 406 of 3 A V 1n .
  • the charges at capacitor s 410-416 are identical, thereby eliminating the need for an equalization stroke.
  • converter 702 the amount of charge displaced is given by expression (902).
  • An interesting aspect of converter 702 is that the energy stored in capacitors 410-416 at the start of the conversion E initia i, given by expression (904), is actually lower than the energy stored at the end of the secondary stroke E en d, given by expression (906). This implies that capacitors 410-416 are being charged during the secondary stroke. An explanation of this is that more energy is extracted from input voltage source 802 than is transferred to output 406 including losses and the energy stored at capacitors 410-416.
  • the extracted energy E 1n is given by expression (908). Again the ripple voltage ⁇ V is the key factor determining the energy balance and the output voltage V ou t similar to expressions (604), (606) and (608).
  • the corresponding expressions are expressions (910), (912) and (914).
  • the equivalent circuit for the primary stroke in converter 702 of the invention looks identical to the equivalent circuit of converter 402. However, there is a very relevant difference in the initial conditions at the start of the primary cycle.
  • capacitors 410-416 are charged to a voltage 1 A V 1n + ⁇ V and they will be discharged to 1 A V 1n while recycling energy C ⁇ VV in back to supply voltage source 802.
  • the current from source 802 to capacitors 410- 416, arranged in series during the primary stroke has a negative polarity.
  • the factor I loaxl /(f C V 1n ) occurring in expressions (916) and (628) has a value of 0.14.
  • Expressions (628) and (916) allow comparing the efficiency of known converter 402 with the efficiency of converter 702 in the invention. With above parameter values, known converter 402 has an efficiency of 81% whereas the converter 702 in the invention has an efficiency of 97%.
  • the ripple voltage ⁇ V for a certain current I out and for a certain frequency f in the invention is lower by a factor of 10 than the ripple voltage ⁇ V in the known converter.
  • the ripple voltage ⁇ V is the determining factor in the energy balance and the energy losses.
  • Both converter 402 and converter 702 require the same number of switches of similar properties to be able to displace charge with sufficient speed within the cycle time.
  • the output voltage in the known converter is lower by an amount of 625 mV (23%), whereas the output voltage in the converter of the invention is lower by an amount of 62.5 mV (i.e. 2.3%).
  • Figs. 10 and 11 are circuit diagrams of another configuration 1000 of a converter in the invention operating in a first phase and in a second phase, respectively.
  • converter 702 capacitors 410-416 were connected in series to input node 404 in the primary stroke and were connected in parallel between input node 404 and output node 406 in the secondary stroke.
  • converter 1000 has capacitors connected in series to output node 406 in a first phase, and in parallel between input node 404 and output node 406 in a second phase.
  • Fig.12 gives formulae roughly explaining the operation of converter 1000 to first order, ignoring the ripple voltage.
  • the voltage across each of capacitors 410-416 is given by expression 1202.
  • the relationship between input voltage V 1n and output voltage V ou t is given by expression (1204).
  • the output voltage V ou t can be expressed as in formula (1206). Again, the result is that the output voltage differs from the input voltage by a factor (1 + n/k).
  • the invention has been explained by way of example, with regard to the drawing enclosed. It is clear to the person skilled in the art that various other configurations of connected capacitors can be used. These other configurations are then variations on the same theme of the invention. For example, the invention has been explained with respect to switching the capacitor configuration between a pure series arrangement and a pure parallel arrangement. It is clear that one or more additional capacitors can be connected in parallel to one or more capacitors of the series configuration, e.g., to cater for a larger capacitance value, and that one or more additional capacitors can be connected in series with one or more of the capacitors in the parallel configuration, e.g., to cater for a smaller capacitance value, without departing from the scope of the invention. Also, the invention can be used with another number of capacitors, e.g., 6 in order to achieve smaller output voltage steps of 1/6 with high efficiency.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

L’invention concerne un convertisseur de tension capacitif (700) comprenant : un nœud d’entrée (404) destiné à recevoir une tension d’entrée (Vin); un nœud de sortie (406) destiné à acheminer une tension de sortie (Vout); un nœud de référence (408) destiné à recevoir une tension de référence; une pluralité de condensateurs (410, 412, 414, 416); et un moyen de commutation (718, 728, 720, 732, 722, 736, 724, 738) configuré pour, dans un premier mode, connecter en série les condensateurs (410, 412, 1414, 416) entre le nœud d’entrée (404) et le nœud de sortie (406), d’une part, et le nœud de référence (408) d’autre part et, dans un deuxième mode, connecter les condensateurs en parallèle entre le nœud d’entrée (404) et le nœud de sortie (406).
PCT/IB2009/051851 2008-05-09 2009-05-06 Convertisseur continu-continu à pompage de charge WO2009136368A1 (fr)

Applications Claiming Priority (2)

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EP08156014.6 2008-05-09
EP08156014 2008-05-09

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WO2009136368A1 true WO2009136368A1 (fr) 2009-11-12

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Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2013043965A3 (fr) * 2011-09-23 2013-06-06 The Penn State Research Foundation Circuit à condensateur pour groupements de sources d'énergie telles que des piles à combustible microbiennes
EP2846448A1 (fr) * 2013-09-06 2015-03-11 Nxp B.V. Convertisseur de puissance à capacités commutées
EP2905885A1 (fr) * 2014-02-07 2015-08-12 Alstom Technology Ltd. Convertisseur CC-CC
CN105308844A (zh) * 2013-09-19 2016-02-03 皇家飞利浦有限公司 具有连续输出调节范围的紧凑功率转换设备
EP3772167A1 (fr) * 2019-07-31 2021-02-03 Nxp B.V. Convertisseur de puissance de condensateur à commutation multiphasé à taux de conversion élevé

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US5596489A (en) * 1994-01-14 1997-01-21 Intel Corporation Capacitive transformer having a switch responsive to clock signals
EP1073185A2 (fr) * 1999-07-27 2001-01-31 Texas Instruments Deutschland Gmbh Convertisseur de courant continu à courant continu
US6198645B1 (en) * 1998-07-02 2001-03-06 National Semiconductor Corporation Buck and boost switched capacitor gain stage with optional shared rest state
US6563235B1 (en) * 2000-10-03 2003-05-13 National Semiconductor Corporation Switched capacitor array circuit for use in DC-DC converter and method
US20060028849A1 (en) * 2004-07-29 2006-02-09 Sanyo Electric Co., Ltd. DC-DC converter
US20070096795A1 (en) * 2005-11-01 2007-05-03 Catalyst Semiconductor, Inc. LED bias current control using adaptive fractional charge pump
US20080094128A1 (en) * 2004-12-03 2008-04-24 Tomoyuki Ito Charge Pump Circuit Driver Circuit Having A Plurality Of Oscillators

Patent Citations (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5596489A (en) * 1994-01-14 1997-01-21 Intel Corporation Capacitive transformer having a switch responsive to clock signals
US6198645B1 (en) * 1998-07-02 2001-03-06 National Semiconductor Corporation Buck and boost switched capacitor gain stage with optional shared rest state
EP1073185A2 (fr) * 1999-07-27 2001-01-31 Texas Instruments Deutschland Gmbh Convertisseur de courant continu à courant continu
US6563235B1 (en) * 2000-10-03 2003-05-13 National Semiconductor Corporation Switched capacitor array circuit for use in DC-DC converter and method
US20060028849A1 (en) * 2004-07-29 2006-02-09 Sanyo Electric Co., Ltd. DC-DC converter
US20080094128A1 (en) * 2004-12-03 2008-04-24 Tomoyuki Ito Charge Pump Circuit Driver Circuit Having A Plurality Of Oscillators
US20070096795A1 (en) * 2005-11-01 2007-05-03 Catalyst Semiconductor, Inc. LED bias current control using adaptive fractional charge pump

Cited By (12)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2013043965A3 (fr) * 2011-09-23 2013-06-06 The Penn State Research Foundation Circuit à condensateur pour groupements de sources d'énergie telles que des piles à combustible microbiennes
US9450437B2 (en) 2011-09-23 2016-09-20 The Penn State University Capacitor circuit for arrays of power sources such as microbial fuel cells
EP2846448A1 (fr) * 2013-09-06 2015-03-11 Nxp B.V. Convertisseur de puissance à capacités commutées
CN104426356A (zh) * 2013-09-06 2015-03-18 恩智浦有限公司 开关电容器功率转换器
US9570976B2 (en) 2013-09-06 2017-02-14 Nxp B.V. Switched capacitor power converter
CN105308844A (zh) * 2013-09-19 2016-02-03 皇家飞利浦有限公司 具有连续输出调节范围的紧凑功率转换设备
EP2905885A1 (fr) * 2014-02-07 2015-08-12 Alstom Technology Ltd. Convertisseur CC-CC
WO2015118114A1 (fr) * 2014-02-07 2015-08-13 Alstom Technology Ltd Convertisseur
CN106464134A (zh) * 2014-02-07 2017-02-22 阿尔斯通技术有限公司 转换器
US10003257B2 (en) 2014-02-07 2018-06-19 Alstom Technology Ltd Converter
EP3772167A1 (fr) * 2019-07-31 2021-02-03 Nxp B.V. Convertisseur de puissance de condensateur à commutation multiphasé à taux de conversion élevé
US10958161B2 (en) 2019-07-31 2021-03-23 Nxp B.V. Multi-phase high conversion ratio switched capacitor power converter

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