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WO1998021819A1 - Generation de frequences pour un dispositif multimode dans un systeme de radiocommunication - Google Patents

Generation de frequences pour un dispositif multimode dans un systeme de radiocommunication Download PDF

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Publication number
WO1998021819A1
WO1998021819A1 PCT/FI1997/000689 FI9700689W WO9821819A1 WO 1998021819 A1 WO1998021819 A1 WO 1998021819A1 FI 9700689 W FI9700689 W FI 9700689W WO 9821819 A1 WO9821819 A1 WO 9821819A1
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WO
WIPO (PCT)
Prior art keywords
khz
mhz
frequency
derived
wideband
Prior art date
Application number
PCT/FI1997/000689
Other languages
English (en)
Inventor
Eero Nikula
Antti Toskala
Harri Holma
Original Assignee
Nokia Mobile Phones Limited
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Nokia Mobile Phones Limited filed Critical Nokia Mobile Phones Limited
Priority to AU50526/98A priority Critical patent/AU5052698A/en
Publication of WO1998021819A1 publication Critical patent/WO1998021819A1/fr

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Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03B—GENERATION OF OSCILLATIONS, DIRECTLY OR BY FREQUENCY-CHANGING, BY CIRCUITS EMPLOYING ACTIVE ELEMENTS WHICH OPERATE IN A NON-SWITCHING MANNER; GENERATION OF NOISE BY SUCH CIRCUITS
    • H03B21/00—Generation of oscillations by combining unmodulated signals of different frequencies
    • H03B21/01—Generation of oscillations by combining unmodulated signals of different frequencies by beating unmodulated signals of different frequencies
    • H03B21/02—Generation of oscillations by combining unmodulated signals of different frequencies by beating unmodulated signals of different frequencies by plural beating, i.e. for frequency synthesis ; Beating in combination with multiplication or division of frequency
    • H03B21/025—Generation of oscillations by combining unmodulated signals of different frequencies by beating unmodulated signals of different frequencies by plural beating, i.e. for frequency synthesis ; Beating in combination with multiplication or division of frequency by repeated mixing in combination with division of frequency only
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H04B1/40—Circuits
    • H04B1/403—Circuits using the same oscillator for generating both the transmitter frequency and the receiver local oscillator frequency

Definitions

  • the invention relates generally to generating internal frequency signals in a radio device.
  • the invention relates particularly to generating frequencies in a multimode device which can operate according to the specifications of several different systems.
  • Digital radio devices require several constant frequency signals at different frequencies. Transmission and reception is usually done by frames, which can be further divided into time slots. Certain clock signals are required to generate and interpret the slots and frames with a correct timing. Timing signals are also required to realize the modulation and demodulation according to bits and/or bit combinations at an agreed bit rate; these timing signals depend on the transmission bit rate and also on the multiple access and modulation methods. Many systems enable the use of several data transmission modes, thus necessitating different bit rates.
  • Figure 1 shows schematically a radio device having a transmitter section 10 and a receiver section 11 which are controlled by a common timing and control block 12 and which use the same frequency synthesizer for generating the radio frequencies.
  • the transmitter section there is connected in series a speech coder 10a, a channel coder 10b, a frame interleaving block 10c, a multiple access implementing block lOd, a modulator lOe and the transmitter radio frequency section lOf, of which the latter is connected through an antenna switch to the antenna 15.
  • the antenna switch 14 can connect the antenna 15 to the receiver's radio frequency section 11a, which is followed by a series connection of an A/D converter l ib, a detector block 1 lc, a deinterleaving block 1 id, a channel decoder 1 le and a speech decoder 1 If.
  • the timing and control block 12 supplies to the multiple access implementing block 1 Od constant frequency signals which synchronize the frames, time slots and symbols (bits or bit combinations), and to the modulator lOe a sampling frequency signal with the aid of which the modulator generates the I and Q modulation signals required by the RF sections.
  • the timing and control block 12 further supplies to the transmitter's radio frequency block lOf the constant frequency signals which align the frames, time slots and the sampling.
  • the frequency synthesizer 13 supplies the PLL (Phase Locked Loop; not separately shown in the figure) reference frequency to the block 12 and generates also the required mixing frequencies for the radio frequency sections lOf and 11a of the transmitter and the receiver.
  • the timing and control block 12 further supplies the A/D converter l ib with a signal which controls the sampling frequency, and the detector block l ie with the synchronizing signals for frames, time slots and symbols.
  • GSM Global System for Mobile telecommunications
  • DCS or DCS 1800 Digital Communications System at 1800 MHz
  • PCN Personal Communications Network
  • D-AMPS Digital Advanced Mobile Phone Service
  • PCS Personal Communications Services
  • Japanese PDC Personal Digital Cellular
  • the third generation system is called FPLMTS (Future Public Land Mobile Telecommunication System) or IMT2000 (International Mobile Telecommunications at 2000 MHz).
  • FPLMTS Full Land Mobile Telecommunication System
  • IMT2000 International Mobile Telecommunications at 2000 MHz.
  • the terminal should also act as a terminal of at least one second generation system in order to have a smooth transition to the new system.
  • Air interface' means all such definitions which have to be made concerning e.g. modulation method, multiple access method, frequency and timing decisions, and data communication rates, so that the communication between a terminal and a base station would be successful.
  • a teirninal operating in several telecommunication systems is generally called a multimode terminal.
  • a multimode terminal In this application we discuss as an exemplary multimode te ⁇ ninal primarily a device which operates as a second generation GSM/DCS terminal and as a third generation UMTS terminal, whereby the UMTS mode particularly means utilization of such wideband commumcation features which are not available in GSM/DCS.
  • TDMA Time Division Multiple Access
  • CDMA Code Division Multiple Access
  • the multimode terminals represent a set of new telecommunications concepts for which it is difficult to find examples in prior art.
  • the most simple and obvious way to design a multimode terminal is to take individual terminals of different systems and to integrate them in a single mechanical entity.
  • Clearly a device resulting from this is clumsy regarding its external features, and disadvantageous regarding manufacturing, because it includes a lot of redundancy on the equipment level.
  • the different systems can partly use the same components. Then a problem arises concerning how to adapt the operation of the same basic parts to the particular requirements of the different systems.
  • One example of the special requirements is the need for constant frequency signals mentioned above.
  • the published international patent application number WO 96/08883 discusses a method for deriving some essential frequencies of a multimode terminal from a single reference oscillator.
  • the terminal is a dual mode radio telephone that may act as a GSM telephone at approximately 900 MHz or a satellite telephone at approximately 1600 MHz.
  • the channel grid frequencies may be derived from a single reference, because the channel grid of the first system (200 kHz) happens to be an integral multiple of the channel grid of the second system ( 3.125 kHz or 5 kHz).
  • the mixing frequencies for intermediate frequency (IF) generation may be derived from a single reference frequency source, because the intermediate frequencies have suitably compatible values.
  • the operation of a multimode radio terminal additionally requires, however, a lot of other constant frequency signals for example in the baseband part of the te ⁇ ninal, and the publication WO 96/08883 does not give any indications about how they should be produced.
  • the object of the invention is to present a method and a device for generating constant frequency signals in a multimode terminal.
  • the object of the invention is that the method and the device according to the invention are advantageous regarding manufacturing, which requires a relatively low number of components.
  • the objects of the invention are attained by deriving the constant frequency signals required by the operation according to different systems from the same reference frequency oscillator signal.
  • the method according to the invention is characterized in that the operating modes of the multimode radio device are a combination of a first mode, which correponds to the operation of a second generation digital cellular radio system, and a second mode, whereby the constant frequency signals required by the first mode are derived from a common reference frequency and the constant frequency signals required by the second mode are results of integral multiplication and/or integral division of the constant frequency signals required by the first mode.
  • the invention also relates to a reference clock circuit arrangement for generating constant frequency signals in a multimode radio device, whose operating modes are a combination of a first mode, which correponds to the operation of a second generation digital cellular radio system, and a second mode.
  • the reference clock circuit arrangement according to the invention is characterized in that it comprises one reference frequency oscillator and integer dividers and/or multipliers for deriving all constant frequency signals required by all operating modes from the common reference frequency generated by the reference frequency oscillator.
  • the invention further relates to a terminal and a base station of a cellular radio system.
  • the terminal and the base station according to the invention are characterized in that they comprise at least one reference clock circuit arrangement like that described above.
  • a common constant frequency reference signal can be used for generating all required constant frequency signals, irrespective of which combination of GSM/DCS functions and wideband communication features of the TDMA type or CDMA type is realized in the multimode terminal.
  • the use of a common reference oscillator essentially simplifies the design and construction of a multimode terminal and a base station, and reduces the power consumption and manufacturing costs, because an accurate reference oscillator is a factor consuming electrical power and is also a relatively expensive component; the prior art use of several parallel oscillators would multiply the costs and power demand for generating the reference frequencies.
  • the radio device has separate reference oscillators for the different systems and for RF, IF and baseband parts, it is inconvenient to change the operating from one system to another, and interference is easily generated at the sum or difference frequencies of the oscillators.
  • the oscillating frequency of the common reference oscillator is 26 MHz, but some embodiments of the invention could also use a reference oscillator at 13 MHz, 39 MHz, 52 MHz or 104 MHz. Almost all required frequencies are obtained from the reference oscillator frequency by a simple integer division, which is an operation easily realized on the component level.
  • a common reference oscillator requires, in order to obtain the greatest advantage, that the time and frequency parameters of the different systems, such as bandwidths, bit rates, frame lengths, time slots, sampling rates and other corresponding factors are selected so that the first system's frequency and/or its integer multiples and integer quotients can be directly used in another system.
  • the GSM/DCS system is examined here as an example of second generation systems, in which the traffic channels are located with 200 kHz spacing on the frequency axis
  • the TDMA version of the UMTS system is proposed to have a bandwidth of 1.6 MHz, which is an integer multiple of 200 kHz.
  • the CDMA based UMTS does not have a bandwidth of 1.6 MHz but an integer multiple of 200 kHz which is higher than the chip frequency.
  • the channel interval is not yet fixed in the same way as in the TDMA and TDMA/CDMA concepts designed to be GSM compatible, but one preferable alternative is a multiple of 1.6 MHz (e.g. 4.8 MHz) which can facilitate frequency allocation in a situation where several air interfaces operate simultaneously.
  • the carrier frequency reference 200 kHz required by the GSM system is obtained directly by integer division from the reference oscillator frequency, and from it the TDMA-UMTS carrier frequency reference 1.6 MHz is easily generated with means well known by a person skilled in the art. Further it is advisable to select the frame length in the UMTS system so that it is the same as in the second generation system (4.615 ms in GSM/DCS) or any fraction or integer multiple of this frame length.
  • Figure 1 shows schematically a known way to use constant frequency signals in a radio device
  • Figure 2 shows a proposed frame structure for the UMTS system
  • Figures 3a to 3e show different ways to divide the time slots of the frame structure
  • Figure 4 shows a preferred principle according to the invention for deriving the frequencies
  • Figure 5 shows in more detail one way to derive the frequencies
  • Figure 6 shows in more detail another way to derive the frequencies
  • Figure 7 shows in more detail a third way to derive the frequencies
  • Figure 8 shows in more detail a fourth way to derive the frequencies
  • Figure 9 shows in more detail a fifth way to derive the frequencies
  • Figure 10 shows in more detail a sixth way to derive the frequencies
  • Figure 11 shows in more detail a seventh way to derive the frequencies
  • Figure 12 shows in more detail an eighth way to derive the frequencies
  • Figure 13 shows in more detail a ninth way to derive the frequencies
  • Figure 14 shows a way to use a different reference frequency.
  • Figure 2 shows a proposed frame structure for the UMTS system using time division multiple access.
  • W-TDMA Wideband Time Division Multiple Access
  • FIG. 2 shows a proposed frame structure for the UMTS system using time division multiple access.
  • the multiple access according to figure 2 is below called W-TDMA (Wideband Time Division Multiple Access).
  • W-TDMA Wideband Time Division Multiple Access
  • FIG and the accompanying figures 3a to 3e are significant to the invention in that they show for which different purposes the constant frequency signals derived according to the invention from a single reference oscillator frequency are required.
  • the length of the frame 20 is selected as 4.615 ms, which is the same as in the GSM system.
  • the frame spans the bandwidth 1.6 MHz, and it is further divided into eight time slots 21 in the same way as in the GSM system. Another possible alternative is to divide the frames into 16 time slots.
  • each time slot can be further divided, when required, into smaller subslots both in the frequency and in the time directions, whereby each subslot of a time slot can be separately allocated to be used by a certain connection.
  • the system provides a possibility to create connections with different communication capacities between the base station and a terminal: the maximum capacity is obtained for a connection which is allocated all time slots 21 of the whole frame 20, and in order of capacity the following connections are those which are allocated one or more complete time slots 21, and the smallest capacity units are subslots of the time slots 21, divided in different ways.
  • a transmitting device which uses a certain time slot or a subslot, transmits information as a burst in this time slot or in this subslot.
  • the so called training sequence must be observed when the available capacity is calculated, the training sequence belonging to each burst and having a certain minimum length, whereby its effect, which decreases the useful capacity, appears particularly in the smallest subslots.
  • the frame length could also be a fraction or an integer multiple of 4.615 milliseconds.
  • a frame with the length 2.308 ms would be half of the GSM/DCS frame length, and it could be divided into three, four, five or six basic time slots, which can be further divided into subslots in the same way as shown in figure 2 and in the figures 3a to 3e below.
  • Digital data communication generally involves time interleaving the frames so that the transmitting device spreads the bits belonging to a certain logical frame into a number of consecutive transmission frames, so that a sudden communication error will not destroy a complete logical frame.
  • the time interleaving can use more transmission frames than in the case of long frames. This is useful if the transmission frequency is changed between the transmission frames (so called frequency hopping); the more frames are used in the time interleaving, the more effectively the time interleaving and frequency hopping can spread the contents of a certain logical frame, and the less a certain sudden error can affect a single logical frame. In some cases it may also be useful to use a longer frame, whose length could be e.g. 9.231 ms (twice the GSM/DCS frame length) or another integer multiple of a known frame length of a second generation system.
  • a longer frame whose length could be e.g. 9.231 ms (twice the GSM/DCS frame length) or another integer multiple of a known frame length of a second generation system.
  • a long frame can facilitate the location of some control structures (the so called logical control channels) in the frame structure, because these channels require a quite low data communication capacity. Reserving a constant time slot or a constant subslot in each frame for the logical control channels can use a too large part of the whole system capacity, if the frame length is short.
  • the data commumcation capacity represented by a frame and its time slots depends i.a. on the modulation method, which can be e.g. Bin-O-QAM (Binary Offset Quadrature Amplitude Modulation) or Quat-O-QAM (Quaternary Offset Amplitude Modulation).
  • the bandwidth efficiency of these methods is assumed as 1.625 bit/s/Hz and 3.25 bit/s/Hz, respectively. Assuming that the last mentioned of these is used, whereby the total capacity of a signal with the bandwidth 1.6 MHz is about 5.2 Mbit/s.
  • the useful communication capacity is about 4.659 Mbit/s for one UMTS carrier with the width of 1.6 MHz.
  • the transmitted information is convolution coded (for instance at a ratio 1/3) and punctured, whereby one could assume that a single UMTS carrier frequency can transmit information between a terminal and a base station at a maximum rate of about 2 Mbit/s. If the concerned carrier frequency is symmetrically time duplexed, then the useful data communication rate is maximum 1 Mbit/s in both directions.
  • the former modulation method (Bin-O-QAM) all capacity values are about one half of those mentioned above.
  • Figures 3a to 3e show five exemplary ways to handle the time slots.
  • the whole time slot 21 is allocated to a single connection, so that according to the above presented reasoning the time slot represents a capacity of about 582 kbit/s (one eighth of 4.659 Mbit/s), when the effects of the convolution coding are disregarded.
  • the time slot 21 is divided into two subslots 30.
  • the time slot 21 is divided into four subslots, of which one subslot 31 for Quat- O-QAM modulation has a capacity of about 132 kbit/s and for Bin-O-QAM modulation about 66 kbit/s, when the effect of the training sequence is observed.
  • the time slot 21 is divided into 8 subslots, whereby the capacity of one subslot 32 roughly corresponds to the capacity of the current GSM system speech slot (in GSM the bandwidth is 200 kHz and the length of the speech time slot is the same as the length of the time slot 21 in figure 3d).
  • the useful data communication capacity of the subslot 32 in figure 3d is estimated as 28.8 kbit/s, where the effects of the training sequence and the suitable punctured convolution coding with the ratio 1/3 are observed.
  • the time slot 21 is divided in the frequency direction into eight subslots, whereby each subslot 33 corresponds, regarding both its bandwidth and duration, to the speech time slot of the current GSM system.
  • time slots in other ways, e.g. in the frequency direction into two, three, five, six, ten or twelve subslots.
  • time slot could be divided according to the invention by the CDMA method, whereby during a certain time slot there are several simultaneous connections spread over the available frequency band with orthogonal or quasi-orthogonal spreading codes.
  • a multimode terminal or base station requires at least the following frequencies:
  • 216.667 Hz frame clock corresponds to the frame length (4.615 ms) 1.733 kHz slot clock, corresponds to the time slot length (0.577 ms) 3.467 kHz slot clock, corresponds to 1/2 time slot length (0.288 ms) 6.933 kHz slot clock, corresponds to 1/4 time slot length (0.144 ms) 13.867 kHz slot clock, corresponds to 1/8 time slot length (0.072 ms) 200 kHz carrier frequency separation according to the GSM system
  • GSM system 2.6 MHz bit/symbol clock corresponding to the 2.6 Mbit/s capacity of the frame using Bin-O-QAM modulation 5.2 MHz bit/symbol clock corresponding to the 5.2 Mbit/s capacity of the frame using Quat-O-QAM modulation.
  • a W-TDMA time slot can be further divided also according to the CDMA principle. It was assumed that the length of one CDMA time unit (the so called chip time) is about 0.462 ⁇ s, which corresponds to a chip frequency of 2.166667 MHz. The sampling in the reception requires at least the double frequency, whereby the list of the required frequencies can be continued with the rows below:
  • 5.2 kHz slot clock corresponds to the length of 1/3 time slot (0.192 ms) 10.4 kHz slot clock, corresponds to the length of 1/6 time slot (0.096 ms) 20.8 kHz slot clock, corresponds to the length of 1/12 time slot (0.048 ms) 8.667 kHz slot clock, corresponds to the length of 1/5 time slot (0.115 ms) 17.333 kHz slot clock, corresponds to the length of 1/10 time slot (0.0577 ms).
  • the frame clocking may require clock signals differing from the above listed:
  • the W-TDMA multiple access the W-CDMA multiple access, in which the available bandwidth is divided with orthogonal or quasi-orthogonal spreading codes between different connections.
  • the required frequencies depend on the system's chip frequency and spreading ratio.
  • the different capacities allocated to different connections are represented by time slots and frequency intervals of different sizes; in a system of the W-CDMA type a high spreading ratio corresponds to a low user data rate on the connection, and vice versa.
  • the minimum spreading ratio is 4 and the maximum spreading ratio 255 or 256.
  • the symbol rate required by a certain spreading ratio is obtained by dividing the system's chip frequency by the spreading ratio. Reception of a code division transmission requires a sampling frequency, which preferably is four or five times the chip frequency.
  • Figure 4 shows a principle according to which the frequencies required by the different modes of a multimode terminal (or base station) are derived from the reference frequency oscillator 40 in different branches.
  • Block 41 illustrates the deriving of those frequencies which are required for the device to be compatible with a second generation digital mobile phone system, such as the GSM.
  • Block 42 illustrates the deriving of those frequencies which are required by the W-TDMA mode
  • block 43 illustrates the deriving of the frequencies for the W-CDMA mode.
  • a versatile UMTS multimode te ⁇ ninal (or base station) all blocks 41, 42 and 43 are realized, whereby the device can operate in the UMTS system, disregarding which multiple access scheme (TDMA or CDMA) is used by the system.
  • TDMA multiple access scheme
  • a simpler system could comprise for instance only the blocks 41 and 42 or the blocks 41 and 43, whereby the narrow band communication services are compatible with the second generation system, and broad band services requiring a high capacity operate in either multiple access scheme.
  • a device having only the blocks 42 and 43, or only one of these A device having only the block 41 co ⁇ esponds to the cmrent second generation devices.
  • the generation of frequencies illustrated by the blocks 41, 42 and 43 are not clearly distinct, but first for instance one of the GSM/DCS frequencies is derived from the oscillator frequency, and then a W-TDMA frequency is further derived from this frequency. Detailed embodiments of the invention in order to derive certain frequencies are discussed more closely below with reference to figures 5 to 13.
  • the basic frequency generated by the oscillator 40 is at least 13 MHz, because this frequency is a common basic frequency in GSM devices and because the main part of the required frequencies can be generated from it by integer division, according to the examples presented below.
  • the most favorable basic frequency of the oscillator 40 was 26 MHz, particularly in a device having a narrow-band communication link compatible towards the second generation (GSM/DCS compatible) and a wideband link of the W-TDMA type. It can also be 39 MHz, 52 MHz or 104 MHz, but higher frequency means a higher power consumption in the oscillator and it increases the interference susceptibility of the oscillator.
  • oscillators one operating at 104 MHz would further be susceptible to interference from the FM frequencies used for broadcasting. Further a signal from oscillators operating at 52 MHz and higher frequencies will produce intermodulation products which interfere with radio signals at 900 MHz and 1800 MHz.
  • Figure 5 shows how constant frequency signals are derived from the 26 MHz reference frequency in a device according to a prefe ⁇ ed embodiment of the invention, which has a na ⁇ ow-band communication link compatible towards the second generation (GSM/DCS compatible) and a wideband link of the W-TDMA type and in which the frame's time slot with the length 0.577 ms is divided into at most eight subslots.
  • the frequency of the oscillator 40 is 26 MHz.
  • Each block 50 to 58 represents a division of the frequency by an integer shown within the block.
  • Figure 6 shows how the constant frequency signals are derived from the reference frequency 13 MHz, when the device in other respects is similar to that in the case of figure 5.
  • the blocks 60 to 63 generate the same frequencies 200 kHz, 2.6 MHz, 361.111 kHz, 346.666 kHz, 325 kHz, 270.833 kHz as the blocks 50 to 53 in figure 5, with the exception that a doubler 62b and a divider 62c are used instead of the single divider 52b of figure 5.
  • the blocks 65 to 68 generate the frequencies 933 kHz, 3.467 kHz, 1.733 kHz and 216.677 Hz in the same way as the blocks 55 to 58 in figure 5.
  • the blocks 62b and 64 do not represent integer divisions but frequency multipliers, which as a device is known per se.
  • Block 62b doubles the 13 MHz reference frequency to 26 MHz and block 64 generates the frequency 13.867 kHz required to clock the 1/8 time slots by multiplying the frequency 6.933 kHz by two.
  • the required clocking of the 1/8 time slots can also be solved by using the frequency 6.933 kHz (for the 1/4 time slot) as a reference and counting symbols (in transmission) or samples (in reception).
  • Figures 7 and 8 show how constant frequency signals are derived from the reference frequency 13 MHz when the device in other respects is similar to that in the case of figure 6, but the W-TDMA time slots are divided into 12 subslots (figure 7) or 10 subslots (figure 8).
  • the blocks 70 to 73 and 80 to 83 co ⁇ espond to the blocks 60 to 63 of figure 6.
  • the blocks 74 to 78 and 84 to 87 are all integer divisions, which result in the required frequencies.
  • Figure 9 shows how constant frequency signals are derived from the reference frequency 13 MHz in a device according to a prefe ⁇ ed embodiment of the invention, which has a narrow-band communication link compatible with the second generation (GSM/DCS compatible) and a wideband link of the W-CDMA type, in which the chip frequency is 4.3333 MHz.
  • Compatibility with GSM/DCS requires a 200 kHz carrier reference, a bit frequency signal 270.833 kHz, a time slot signal 1.733 kHz and a frame clock signal 216.667 Hz. These are generated in the blocks 90, 91, 92, 93 and 94.
  • the block 95 divides the 200 kHz ca ⁇ ier frequency reference signal by 2000 in order to generate the CDMA frame alignment signal of 100 Hz (the CDMA frame length is here assumed to be 10 ms).
  • the block 96 generates the chip frequency 4.3333 MHz and the block 97 contains alternative integer divisors co ⁇ esponding to the spreading ratios 4, 8, 16, 32, 64, 128 and 256 which generate the symbol rates 1083.333 kHz, 541.667 kHz, 270.833 kHz, 135.417 kHz, 67.708 kHz, 33.854 kHz and 16.927 kHz.
  • the spreading ratio 256 can be replaced by the spreading ratio 255 in down- link communication, whereby the co ⁇ esponding symbol rate is 16.993 kHz.
  • Figure 10 co ⁇ esponds to figure 9 in other respects, but the frequency of the oscillator 40 is 26 MHz and the chip frequency is 5.2 MHz. Due to the higher chip frequency the symbol rates co ⁇ esponding to the different spreading ratios are also higher than in figure 9.
  • the block 100 divides the oscillator frequency by two, and then the blocks 101 to 106 generate the same frequencies as the blocks 90 to 95 in figure by using the same divisions.
  • the block 107 generates the chip frequency 5.2 MHz and the block 108 contains alternative integer divisors co ⁇ esponding to the spreading ratios 4, 8, 16, 32, 64, 128 and 256 which produce the symbol rates 1300 kHz, 650 kHz, 325 kHz, 162.5 kHz, 81.25 kHz, 40.625 kHz and 20.3125 kHz. Also in this case the spreading ratio 256 can be replaced by the spreading ratio 255 in downlink communication, whereby the co ⁇ esponding symbol rate is 20.392 kHz.
  • Figure 11 shows a combination of the embodiments in figures 9 and 10.
  • the frequency of the oscillator 40 is 26 MHz and the blocks 110 to 116 generate from it frequencies by the same operations as the blocks 100 to 106 in figure 10.
  • the block 117 divides the oscillator frequency by 6, whereby the chip frequency will be 4.3333 MHz, in the same way as in figure 9.
  • the integer divisions contained in block 118 generate the same frequencies co ⁇ esponding to the same spreading ratios as the block 97 in figure 9.
  • Figure 12 shows how the constant frequency signals are derived from the reference frequency 39 MHz in a triple mode multimode device having all functions represented by the blocks 41, 42 and 43 in figure 4.
  • the block 40 is a 39 MHz oscillator.
  • the block 120 generates by a direct integer division the 4.333 MHz sampling frequency for the W-TDMA-CDMA function.
  • the other GSM/DCS and W-TDMA frequencies are derived from the frequency 13 MHz, which is generated by the block 121.
  • the block 132 generates the chip frequency 2.166667 MHz for the W-TDMA- CDMA function.
  • the block 131 generates the frequency 100 Hz which co ⁇ esponds to the frame length 10 ms used by the W-CDMA function.
  • the W-CDMA section in figure 12 supports two alternative chip frequencies, which are 4.875 Mchip/s and 9.75 Mchip/s.
  • the quadruple sampling frequency 39 MHz co ⁇ esponding to the latter chip frequency is obtained directly from the oscillator 40.
  • the quadruple sampling frequency (19.5 MHz) co ⁇ esponding to the former chip frequency is obtained from block 133.
  • the real chip frequencies are obtained from the blocks 134 and 136, and the block 135 generates the symbol rates 19.080235 kHz and 38.235294 kHz co ⁇ esponding to the spreading ratios 511 and 255.
  • the block 137 Co ⁇ espondingly the block 137 generates the symbol rate 19.117647 kHz co ⁇ esponding to the spreading rate 255 at the lower chip frequency.
  • the highest spreading ratios (511 at the higher and 255 at the lower chip frequency) are here intended particularly to be used for the downlink, or for the transmission from the base station to the terminal. When required it is also possible to use the spreading ratio 256.
  • the block 138 contains several alternative integer divisions co ⁇ esponding to the spreading ratios 2, 4, 8, 16, 32, 64, 128 and 256.
  • the co ⁇ esponding symbol rates are in order 2.4375 MHz, 1.21875 MHz, 609.375 kHz, 304.6875 kHz, 152.34375 kHz, 76.171875 kHz, 38.085938 kHz and 19.042969 kHz.
  • Figure 13 shows how the constant frequency signals are derived from the reference frequency 26 MHz in a triple mode multimode device. Particularly regarding W-
  • TDMA this is a more advantageous embodiment than that of figure 12 presented above, because also the clock frequency for the 1/8 time slot is obtained by integer division from the reference frequency.
  • the block 140 co ⁇ esponds to the block 120 of figure 12, however so that the divisor is 6 and not 9.
  • the block 141 generates the frequency 2.6 MHz directly from the reference frequency by one division, and the block 142 generates the desired clock frequency for the 1/8 time slot, also by one division.
  • the block 143 generates from the reference frequency a signal of 13
  • the highest frequency for the W-CDMA function is the oscillator's frequency 26 MHz, which is used in the embodiment of figure 13 as a fivefold sampling frequency co ⁇ esponding to the 5.2 MHz chip frequency (block 153).
  • the block 154 generates the symbol rates 1300 kHz, 650 kHz, 325 kHz, 162.5 kHz, 81.25 kHz, 40.625 kHz, 20.3125 kHz and 20.392157 kHz co ⁇ esponding to the spreading ratios 4, 8, 16, 32, 64, 128, 256 and 255.
  • the spreading ratio 255 is most preferably used for the downlink transmission, but it can also use the spreading ratio 256.
  • a frame can also have another length than the 4.615 ms known from GSM/DCS.
  • the frequency 433.333 Hz co ⁇ esponding to a frame with the half length (2.308 ms) is in the embodiments of figures 5 to 13 most advantageously obtained from that block which generates the frequency 1.733 kHz co ⁇ esponding to the time slot length 0.577 ms (blocks 57, 67, 77, 86, 103, 113, 126 and 146) by further dividing by four the frequency generated by that block.
  • the frequency 108.333 Hz co ⁇ esponding to the double frame length (9.231 ms) is co ⁇ espondingly most advantageously obtained from the block which generates the frequency 216.667 Hs co ⁇ esponding to the frame length 4.615 ms (blocks 58, 68, 78, 87, 93, 104, 114, 131 and 147) by further dividing by two the frequency generated by that block.
  • FIG. 14 shows the generation of a 13 MHz frequency and a 16.384 MHz frequency from the output of a 19.2 MHz reference oscillator 155.
  • the former requires division by 96 in block 156 and multiplication by 65 in block 157, and the latter requires division by 75 in block 158 and multiplication by 64 in block 159.
  • the oversampling frequencies of the other chip rates are easily generated from the 16.384 MHz frequency through doubling.
  • the oversampling frequency does not have to be four times the chip rate; in many cases a lower oversampling frequency is sufficient.
  • the embodiments presented above cover a very large number of frequencies and ways to generate them. If the system specifications do not require a certain terminal or base station to use a certain frequency mentioned in the above description, the generation of this frequency could simply be omitted. Similarly the generation of all frequencies (e.g. the Enhanced GSM frequencies) is not shown in each embodiment, but their generation can be readily added by comparing the discussed embodiments with each other.
  • Figure 5 shows how the Enhanced GSM frequencies can be derived from a 26 MHz reference frequency and figure 6 shows how they can be derived from a 13 MHz reference frequency or a 13 MHz frequency that is a result of an integral division and/or multiplication of some other reference frequency.
  • the divisors and/or multipliers shown in the figures presenting the detailed embodiments can be combined, if required. If for instance a frequency X is obtained from a frequency Y by dividing it first by 2 and then by 3, the invention does not require these divisions to be separate operations: in order to generate the frequency X the frequency Y can be directly divided by 6. Similarly, the divisors can be divided into their factors. If for instance a frequency XX is obtained from a frequency YY by dividing it by 9, and a frequency ZZ is obtained from the same frequency YY by dividing it first by 3 and then by 6, then a common predivider with the divisor 3 can be used for both. Thus the frequency XX is obtained from YY by dividing it first by 3 and then by 3, and ZZ is obtained from YY dividing it first by 3 and then by 6.
  • the invention shows how one constant frequency reference oscillator can be used in a simple way to generate all required constant frequency signals in a multimode terminal (or base station). In this way one can avoid the need for several oscillators and the increase in manufacturing costs and power consumption caused by this. Further it eliminates the inconveniences relating to a change of the oscillator during use.
  • the reference clock arrangement according to the invention could naturally also be used in a radio device which has only one operating mode, but which is intended to operate in a multimode compatible system.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Mobile Radio Communication Systems (AREA)

Abstract

Dans un dispositif de radiocommunication multimode, dont les modes de fonctionnement sont une combinaison de GSM/DCS, d'AMRT à bande large et d'AMRC à bande large, tous les signaux de fréquence constante nécessaires sont générés à partir d'une fréquence générée par un oscillateur commun (40) à fréquence de référence. Les fréquences sont générées par division entière et éventuellement par des multiplicateurs de fréquence nécessaires supplémentaires.
PCT/FI1997/000689 1996-11-14 1997-11-13 Generation de frequences pour un dispositif multimode dans un systeme de radiocommunication WO1998021819A1 (fr)

Priority Applications (1)

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AU50526/98A AU5052698A (en) 1996-11-14 1997-11-13 Generating frequencies for a multimode device of a radio system

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FI964559A FI102122B (fi) 1996-11-14 1996-11-14 Radiojärjestelmän monimoodilaitteen taajuuksien generointi
FI964559 1996-11-14

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WO2002021688A1 (fr) * 2000-09-07 2002-03-14 Siemens Aktiengesellschaft Procede et dispositif pour convertir une frequence d'echantillonnage en systemes multistandards
EP1213830A1 (fr) * 2000-12-07 2002-06-12 Motorola, Inc. Dispositif multi-mode de radiocommunications utilisant un oscillateur de référence commun
WO2002073820A1 (fr) * 2001-03-08 2002-09-19 Infineon Technologies Ag Systeme de commande de synchronisation pour des systemes de communication mobiles
EP1097535A4 (fr) * 1998-07-10 2005-04-06 Hyundai Electronics America Emetteur-recepteur sans fil ameliore et plan de frequences
WO2006012275A1 (fr) * 2004-06-30 2006-02-02 Silicon Laboratories Inc. Architecture de trajet de transmission ratiometrique pour des systemes de communication
US7272373B2 (en) 2004-06-30 2007-09-18 Silacon Laboratories Inc. Ratiometric clock systems for integrated receivers and associated methods
US7376396B2 (en) 2004-06-30 2008-05-20 Silicon Laboratories Inc. Ratiometric transmit path architecture for communication systems
US7376399B2 (en) 2004-06-30 2008-05-20 Silicon Laboratories Inc. Weighted mixing circuitry for quadrature processing in communication systems
US7835706B2 (en) 2004-06-30 2010-11-16 Silicon Laboratories, Inc. Local oscillator (LO) port linearization for communication system with ratiometric transmit path architecture
EP1807989B1 (fr) * 2004-10-12 2017-06-14 Intel Corporation Systemes et procedes pour recepteur en faible frequence intermediaire (fi)

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EP0186068A1 (fr) * 1984-12-19 1986-07-02 Telefongyar Montage pour produire des fréquences porteuses de canaux, des fréquences auxiliaires pilotes, des fréquences porteuses de système et des fréquences de contrôle pour système de porteuses dans des systèmes de téléphone multicanaux à courants porteurs avec système de prémodulation
EP0581573A1 (fr) * 1992-07-28 1994-02-02 Nokia Mobile Phones Ltd. Radiotéléphone universel
EP0678974A2 (fr) * 1994-04-21 1995-10-25 Nokia Mobile Phones Ltd. Emetteur et/ou récepteur
WO1996008883A1 (fr) * 1994-09-14 1996-03-21 Ericsson Inc. Satellite/telephone cellulaire a deux modes a synthetiseur de frequences
EP0729238A2 (fr) * 1995-02-08 1996-08-28 Sony Corporation Emetteur et émetteur-récepteur

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EP0186068A1 (fr) * 1984-12-19 1986-07-02 Telefongyar Montage pour produire des fréquences porteuses de canaux, des fréquences auxiliaires pilotes, des fréquences porteuses de système et des fréquences de contrôle pour système de porteuses dans des systèmes de téléphone multicanaux à courants porteurs avec système de prémodulation
EP0581573A1 (fr) * 1992-07-28 1994-02-02 Nokia Mobile Phones Ltd. Radiotéléphone universel
EP0678974A2 (fr) * 1994-04-21 1995-10-25 Nokia Mobile Phones Ltd. Emetteur et/ou récepteur
WO1996008883A1 (fr) * 1994-09-14 1996-03-21 Ericsson Inc. Satellite/telephone cellulaire a deux modes a synthetiseur de frequences
EP0729238A2 (fr) * 1995-02-08 1996-08-28 Sony Corporation Emetteur et émetteur-récepteur

Cited By (14)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP1097535A4 (fr) * 1998-07-10 2005-04-06 Hyundai Electronics America Emetteur-recepteur sans fil ameliore et plan de frequences
WO2002021688A1 (fr) * 2000-09-07 2002-03-14 Siemens Aktiengesellschaft Procede et dispositif pour convertir une frequence d'echantillonnage en systemes multistandards
US7039438B2 (en) 2000-12-07 2006-05-02 Freescale Semiconductor, Inc. Multi-mode radio communications device using a common reference oscillator
EP1213830A1 (fr) * 2000-12-07 2002-06-12 Motorola, Inc. Dispositif multi-mode de radiocommunications utilisant un oscillateur de référence commun
WO2002047247A1 (fr) * 2000-12-07 2002-06-13 Motorola Inc. Appareil de communication radio multimode utilisant un oscillateur a reference classique
WO2002073820A1 (fr) * 2001-03-08 2002-09-19 Infineon Technologies Ag Systeme de commande de synchronisation pour des systemes de communication mobiles
US7433436B2 (en) 2001-03-08 2008-10-07 Infineon Technologies Ag Timing control configuration and method for mobile communications systems
WO2006012275A1 (fr) * 2004-06-30 2006-02-02 Silicon Laboratories Inc. Architecture de trajet de transmission ratiometrique pour des systemes de communication
US7272373B2 (en) 2004-06-30 2007-09-18 Silacon Laboratories Inc. Ratiometric clock systems for integrated receivers and associated methods
US7376396B2 (en) 2004-06-30 2008-05-20 Silicon Laboratories Inc. Ratiometric transmit path architecture for communication systems
US7376399B2 (en) 2004-06-30 2008-05-20 Silicon Laboratories Inc. Weighted mixing circuitry for quadrature processing in communication systems
US7471940B2 (en) 2004-06-30 2008-12-30 Silicon Laboratories Inc. Ratiometric clock systems for integrated receivers and associated methods
US7835706B2 (en) 2004-06-30 2010-11-16 Silicon Laboratories, Inc. Local oscillator (LO) port linearization for communication system with ratiometric transmit path architecture
EP1807989B1 (fr) * 2004-10-12 2017-06-14 Intel Corporation Systemes et procedes pour recepteur en faible frequence intermediaire (fi)

Also Published As

Publication number Publication date
FI102122B1 (fi) 1998-10-15
FI964559A0 (fi) 1996-11-14
FI964559L (fi) 1998-05-15
AU5052698A (en) 1998-06-03
FI102122B (fi) 1998-10-15

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